®

INA110

Fast-Settling FET-Input
INSTRUMENTATION AMPLIFIER

FEATURES APPLICATIONS
● LOW BIAS CURRENT: 50pA max ● MULTIPLEXED INPUT DATA
● FAST SETTLING: 4µs to 0.01% ACQUISITION SYSTEM
● HIGH CMR: 106dB min; 90dB at 10kHz ● FAST DIFFERENTIAL PULSE AMPLIFIER
● INTERNAL GAINS: 1, 10, 100, 200, 500 ● HIGH SPEED GAIN BLOCK
● VERY LOW GAIN DRIFT: 10 to 50ppm/°C ● AMPLIFICATION OF HIGH IMPEDANCE
SOURCES
● LOW OFFSET DRIFT: 2µV/°C
● LOW COST
● PINOUT SIMILAR TO AD524 AND AD624

DESCRIPTION FET INA110

1 Input
The INA110 is a versatile monolithic FET-input –In
13 4.44kΩ 10kΩ 10kΩ 10
instrumentation amplifier. Its current-feedback circuit X 10 A1 Sense
404Ω
topology and laser trimmed input stage provide X 100
12

excellent dynamic performance and accuracy. The (1)

16 201Ω 20kΩ
X 200
INA110 settles in 4µs to 0.01%, making it ideal for
80.2Ω 9
11
high speed or multiplexed-input data acquisition X 500
A3 Output
20kΩ
systems.
Internal gain-set resistors are provided for gains of 1, 3
RG
10, 100, 200, and 500V/V. Inputs are protected for A2
10kΩ 10kΩ 6
Ref
differential and common-mode voltages up to ±VCC. 2
+In
Its very high input impedance and low input bias FET
current make the INA110 ideal for applications Input

requiring input filters or input protection circuitry. 4 5 8 7 14 15

Input +VCC –VCC Output

The INA110 is available in 16-pin plastic and ceramic Offset Offset
DIPs, and in the SOL-16 surface-mount package. Adjust Adjust

Military, industrial and commercial temperature range

NOTE: (1) Connect to RG for desired gain.
grades are available.

International Airport Industrial Park • Mailing Address: PO Box 11400 • Tucson, AZ 85734 • Street Address: 6730 S. Tucson Blvd. • Tucson, AZ 85706
Tel: (520) 746-1111 • Twx: 910-952-1111 • Cable: BBRCORP • Telex: 066-6491 • FAX: (520) 889-1510 • Immediate Product Info: (800) 548-6132

©
1986 Burr-Brown Corporation PDS-645E Printed in U.S.A. September, 1993
SPECIFICATIONS
ELECTRICAL
At +25°C, ±VCC = 15VDC, and RL = 2kΩ, unless otherwise specified.

INA110AG INA110BG, SG INA110KP, KU

PARAMETER CONDITIONS MIN TYP MAX MIN TYP MAX MIN TYP MAX UNITS
GAIN
Range of Gain 1 800 * * * * V/V
Gain Equation(1) * G = 1 + [40k/(RG + 50Ω)] * V/V
Gain Error, DC: G = 1 0.002 0.04 * 0.02 * * %
G = 10 0.01 0.1 0.005 0.05 * * %
G = 100 0.02 0.2 0.01 0.1 * * %
G = 200 0.04 0.4 0.02 0.2 * * %
G = 500 0.1 1 0.05 0.5 * * %
Gain Temp. Coefficient: G = 1 ±3 ±20 * ±10 * ppm/°C
G = 10 ±4 ±20 ±2 ±10 * ppm/°C
G = 100 ±6 ±40 ±3 ±20 * ppm/°C
G = 200 ±10 ±60 ±5 ±30 * ppm/°C
G = 500 ±25 ±100 ±10 ±50 * ppm/°C
Nonlinearity, DC: G = 1 ±0.001 ±0.01 ±0.0005 ±0.005 * * % of FS
G = 10 ±0.002 ±0.01 ±0.001 ±0.005 * * % of FS
G = 100 ±0.004 ±0.02 ±0.002 ±0.01 * * % of FS
G = 200 ±0.006 ±0.02 ±0.003 ±0.01 * * % of FS
G = 500 ±0.01 ±0.04 ±0.005 ±0.02 * * % of FS
OUTPUT
Voltage, RL = 2kΩ Over Temperature ±10 ±12.7 * * * * V
Current Over Temperature ±5 ±25 * * * * mA
Short-Circuit Current ±25 * * mA
Capacitive Load Stability 5000 * * pF
INPUT OFFSET VOLTAGE(2)
Initial Offset: G, P ±(100 + ±(500 + ±(50 + ±(250 + * * µV
1000/G) 5000/G) 600/G) 3000/G)
U ±(200 + ±(1000 + µV
2000/G) 5000/G)
vs Temperature ±(2 + ±(5 + ±(1 + ±(2 + * µV/°C
20/G) 100/G) 10/G) 50/G)
vs Supply VCC = ±6V to ±18V ±(4 + ±(30 + ±(2 + ±(10 + * * µV/V
60/G) 300/G) 30/G) 180/G)
BIAS CURRENT
Initial Bias Current Each Input 20 100 10 50 * * pA
Initial Offset Current 2 50 1 25 * * pA
Impedance: Differential 5x1012||6 * * Ω || pF
Common-Mode 2x1012||1 * * Ω || pF
VOLTAGE RANGE VIN Diff. = 0V(3)
Range, Linear Response ±10 ±12 * * V
CMR with 1kΩ Source Imbalance:
G=1 DC 70 90 80 100 * * dB
G = 10 DC 87 104 96 112 * * dB
G = 100 DC 100 110 106 116 * * dB
G = 200 DC 100 110 106 116 * * dB
G = 500 DC 100 110 106 116 * * dB
INPUT NOISE(4)
Voltage, fO = 10kHz 10 * * nV/√Hz
fB = 0.1Hz to 10Hz 1 * * µVp-p
Current, fO = 10kHz 1.8 * * fA/√Hz
OUTPUT NOISE(4)
Voltage, fO = 10kHz 65 * * nV/√Hz
fB = 0.1Hz to 10Hz 8 * * µVp-p
DYNAMIC RESPONSE
Small Signal: G = 1 –3dB 2.5 * * MHz
G = 10 2.5 * * MHz
G = 100 470 * * kHz
G = 200 240 * * kHz
G = 500 100 * * kHz
Full Power VOUT = ±10V,
G = 2 to 100 190 270 * * * * kHz
Slew Rate G = 2 to 100 12 17 * * * * V/µs
Settling Time:
0.1%, G = 1 VO = 20V Step 4 * * µs
G = 10 2 * * µs
G = 100 3 * * µs
G = 200 5 * * µs
G = 500 11 * * µs

INA110 2
SPECIFICATIONS (CONT)
ELECTRICAL
At +25°C, ±VCC 15VDC, and RL = 2KΩ, unless otherwise specified.

INA110AG INA110BG, SG INA110KP, KU

PARAMETER CONDITIONS MIN TYP MAX MIN TYP MAX MIN TYP MAX UNITS
DYNAMIC RESPONSE (CONT)
Settling Time:
0.01%,G = 1 VO = 20V Step 5 12.5 * * * µs
G = 10 3 7.5 * * * µs
G = 100 4 7.5 * * * µs
G = 200 7 12.5 * * * µs
G = 500 16 25 * * * µs
Recovery(5) 50% Overdrive 1 * * µs
POWER SUPPLY
Rated Voltage ±15 * * V
Voltage Range ±6 ±18 * * * * V
Quiescent Current VO = 0V ±3 ±4.5 * * * * mA
TEMPERATURE RANGE
Specification: A, B, K –25 +85 * * 0 +70 °C
S –55 +125 °C
Operation –55 +125 * * –25 +85 °C
Storage –65 +150 * * –40 +85 °C
θJA 100 * * °C/W

* Same as INA110AG.
NOTES: (1) Gains other than 1, 10, 100, 200, and 500 can be set by adding an external resistor, RG, between pin 3 and pins 11, 12 and 16. Gain accuracy is a function
of RG and the internal resistors which have a ±20% tolerance with 20ppm/°C drift. (2) Adjustable to zero. (3) For differential input voltage other than zero, see Typical
Performance Curves. (4) VNOISE RTI = √VN2 INPUT + (VN OUTPUT/Gain)2. (5) Time required for output to return from saturation to linear operation following the removal of
an input overdrive voltage.

PIN CONFIGURATION ABSOLUTE MAXIMUM RATINGS

Top View DIP/SOIC Supply Voltage .................................................................................. ±18V
Input Voltage Range .......................................................................... ±VCC
Operating Temperature Range: G ................................. –55°C to +125°C
–In 1 16 x200 P, U ............................... –25°C to +85°C
Storage Temperature Range: G .................................... –65°C to +150°C
+In 2 15 Output Offset Adj.
P, U .................................. –40°C to +85°C
RG 3 14 Output Offset Adj. Lead Temperature (soldering, 10s): G, P ..................................... +300°C
(soldering, 3s): U ........................................... +260°C
Input Offset Adj. 4 13 x10 Output Short Circuit Duration ............................... Continuous to Common

Input Offset Adj. 5 12 x100

Reference 6 11 x500 PACKAGE INFORMATION

10 Output Sense PACKAGE DRAWING
–VCC 7
MODEL PACKAGE NUMBER(1)
+VCC 8 9 Output INA110AG 16-Pin Ceramic DIP 109
INA110BG 16-Pin Ceramic DIP 109
INA110SG 16-Pin Ceramic DIP 109
INA110KP 16-Pin Plastic DIP 180
INA110KU SOL-16 SOIC 211
NOTE: (1) For detailed drawing and dimension table, please see end of data
sheet, or Appendix D of Burr-Brown IC Data Book.

ORDERING INFORMATION

MODEL PACKAGE TEMPERATURE RANGE

INA110AG 16-Pin Ceramic DIP –25°C to +85°C

INA110BG 16-Pin Ceramic DIP –25°C to +85°C
INA110SG 16-Pin Ceramic DIP –55°C to +125°C
INA110KP 16-Pin Plastic DIP 0°C to +70°C
INA110KU SOL-16 SOIC 0°C to +70°C

The information provided herein is believed to be reliable; however, BURR-BROWN assumes no responsibility for inaccuracies or omissions. BURR-BROWN
assumes no responsibility for the use of this information, and all use of such information shall be entirely at the user’s own risk. Prices and specifications are subject
to change without notice. No patent rights or licenses to any of the circuits described herein are implied or granted to any third party. BURR-BROWN does not
authorize or warrant any BURR-BROWN product for use in life support devices and/or systems.

3 INA110
DICE INFORMATION
PAD FUNCTION
1 –In
2 +In
3A,3B RG (connect both)
15 14 13 12 11 4 Input Offset Adjust
10
5 Input Offset Adjust
16 6 Reference
7 –VCC
9 8 +VCC
9 Output
1
10 Output Sense
11 x500
12 x100
13 x10
8 14 Output Offset Adjust
2 15 Output Offset Adjust
7 16 x200
Pads 3A and 3B must be connected.
5 Substrate Bias: Internally connected to –VCC power sup-
3A 3B 4 6 ply.
7
MECHANICAL INFORMATION
MILS (0.001") MILLIMETERS
INA110 DIE TOPOGRAPHY Die Size 139 x 89 ±5 3.53 x 2.26 ±0.13
Die Thickness 20 ±3 0.51 ±0.08
Min. Pad Size 4x4 0.10 x 0.10
Backing Gold

TYPICAL PERFORMANCE CURVES

At TA = +25°C, and ±VCC = 15VDC, unless otherwise noted.

INPUT VOLTAGE RANGE vs SUPPLY OUTPUT SWING vs SUPPLY

±15 ±16
Input Voltage Range (V)

±12 ±13
Output Voltage (V)

RL = 2kΩ

±9 ±10

±6 ±7

±3 ±4
±6 ±9 ±12 ±15 ±18 ±6 ±9 ±12 ±15 ±18

Power Supply Voltage (V) Power Supply Voltage (V)

OUTPUT SWING vs LOAD RESISTANCE BIAS CURRENT vs SUPPLY

±16 25

20
Input Bias Current (pA)

±12
Output Voltage (V)

15
±8
10

±4
5

0 0
0 400 800 1.2k 1.6k 2M ±6 ±9 ±12 ±15 ±18
Load Resistance (Ω) Power Supply Voltage (V)

INA110 4
TYPICAL PERFORMANCE CURVES (CONT)
TA = +25°C, ±VCC = 15VDC, unless otherwise noted.

BIAS CURRENT vs TEMPERATURE GAIN vs FREQUENCY

100nA 1k
G = 500

10nA G = 200
Input Bias Current

G = 100
100

Gain (V/V)
1pA

100pA G = 10
10

10pA

1pA 1 G=1

–55 –25 5 35 65 95 125 10 100 1k 10k 100k 1M 10M

Temperature (°C) Frequency (Hz)

CMR vs FREQUENCY POWER SUPPLY REJECTION vs FREQUENCY

120 120
G = 500 G = 500
Common-Mode Rejection (dB)

Power Supply Rejection (dB)

100 100
G = 200 G = 200
80 80
G = 100 G = 100
60 60
G = 10 G = 10
40 40
G=1 G=1

20 20

0 0
1 10 100 1k 10k 100k 1M 1 10 100 1k 10k 100k 1M
Frequency (Hz) Frequency (Hz)

LARGE SIGNAL TRANSIENT RESPONSE SMALL SIGNAL TRANSIENT RESPONSE

(G = 100) (G = 100)

10 100
Output Voltage (V)

Output Voltage (V)

0 0

–10 –100

0 10 20 0 10 20
Time (µs) Time (µs)

5 INA110
TYPICAL PERFORMANCE CURVES (CONT)
TA = +25°C, ±VCC = 15VDC, unless otherwise noted.

SETTLING TIME vs GAIN

(0.01%, 20V Step) OUTPUT NOISE VOLTAGE vs FREQUENCY
20 1000

Output Noise Voltage (nV/√Hz)

500
15
Settling Time (µs)

200

10 100

50
5
20

0 10
1 10 100 1k 1 10 100 1k 10k
Gain (V/V) Frequency (Hz)

COMMON-MODE VOLTAGE vs
INPUT NOISE VOLTAGE vs FREQUENCY DIFFERENTIAL INPUT VOLTAGE
100 12

50
Input Noise Voltage (nV/√Hz)

Common-Mode Voltage (V)

9
20

10 6

5
3
2

1 0
1 10 100 1k 10k 0 3 6 9 12
Frequency (Hz) Differential Input Voltage x Gain (V) = VO

WARM-UP DRIFT vs TIME

50
Change In Input Offset Voltage (µV)

40

30

20

10

0
0 1 2 3 4 5
Time (minutes)

INA110 6
DISCUSSION OF INA110’s input (RTI) is the offset of the input stage plus
the offset of the output stage divided by the gain of the
PERFORMANCE input stage. This allows specification of offset independent
A simplified diagram of the INA110 is shown on the first of gain.
page. The design consists of the classical three operational
amplifier configuration using current-feedback type op amps
+VCC –VCC
with precision FET buffers on the input. The result is an Input Output
instrumentation amplifier with premium performance not Offset Offset
Adjust Adjust
normally found in integrated circuits.
100kΩ 100kΩ
The input section (A1 and A2) incorporates high perfor- 4
mance, low bias current, and low drift amplifier circuitry. 1
5
14
The amplifiers are connected in the noninverting configura- 15
10
tion to provide high input impedance (1012Ω). Laser-trim- ∆VIN INA110
9 VOUT
ming is used to achieve low offset voltage. Input cascoding 2
assures low bias current and high CMR. Thin-film resistors 6
on the integrated circuit provide excellent gain accuracy and
temperature stability.
The output section (A3) is connected in a unity-gain differ-
ence amplifier configuration. Precision matching of the four FIGURE 2. Offset Adjustment Circuit.
10kΩ resistors, especially over temperature and time,
assures high common-mode rejection. For systems using computer autozeroing techniques, neither
offset nor offset drift are of concern. In many other applica-
BASIC POWER SUPPLY tions, the factory-trimmed offset gives excellent results.
AND SIGNAL CONNECTIONS When greater accuracy is desired, one adjustment is usually
sufficient. In high gains (>100) adjust only the input offset,
Figure 1 shows the proper connections for power supply and
and in low gains the output offset. For higher precision in all
signal. Supplies should be decoupled with 1µF tantalum
gains, both can be adjusted by first selecting high gain and
capacitors as close to the amplifier as possible. To avoid
adjusting input offset and then low gain and adjusting output
gain and CMR errors introduced by the external circuit,
offset. The offset adjustment will, however, add to the drift
connect grounds as indicated, being sure to minimize ground
by approximately 0.33µV/°C per 100µV of input offset
resistance. Resistance in series with the reference (pin 6)
voltage that is adjusted. Therefore, care should be taken
will degrade CMR. To maintain stability, avoid capacitance
when considering use of adjustment.
from the output to the gain set, offset adjust, and input pins.
Output offsetting can be accomplished as shown in Figure 3
by applying a voltage to the reference (pin 6) through a
buffer. This limits the resistance in series with pin 6 to
minimize CMR error. Be certain to keep this resistance low.
1
13 Sense Note that the offset error can be adjusted at this reference
x10
x100
12 10 point with no appreciable degradation in offset drift.
∆VIN 16 INA110 9 VOUT
x200
11
x500 6
3 RL
2 8
7
1µF 1
10 VOUT
VOUT = ∆VIN G 9
∆VIN INA110
+VCC
+VCC 2 6

–VCC 1µF R1

R2
OPA177 –VCC
VOFFSETTING

FIGURE 1. Basic Circuit Connection. VOFFSETTING R3

VOUT = VOFFSETTING + ∆VIN G.
With ±VCC = 15V, R1 = 100kΩ, R2 = 1MΩ.
OFFSET ADJUSTMENT R3 = 10kΩ, VOFFSETTING = ±150mV.
Figure 2 shows the offset adjustment circuit for the INA110.
Both the offset of the input stage and output stage can be
adjusted separately. Notice that the offset referred to the FIGURE 3. Output Offsetting.

7 INA110
GAIN SELECTION are eliminated since they are inside the feedback loop.
Gain selection is accomplished by connecting the appropri- Proper connection is shown in Figure 1. When more current
ate pins together on the INA110. Table I shows possible is to be supplied, a power booster can be placed within the
gains from the internal resistors. Keep the connections as feedback loop as shown in Figure 5. Buffer errors are
short as possible to maintain accuracy. minimized by the loop gain of the output amplifier.

CONNECT PIN 3 GAIN GAIN

R1
GAIN TO PIN ACCURACY (%) DRIFT (ppm/°C)
The following gains have guaranteed accuracy:
1 none 0.02 10 1
R2
10 13 0.05 10 10 VOUT
100 12 0.1 20 ∆VIN 9
INA110
200 16 0.2 30 6
500 11 0.5 50 2
Output Stage Gain
The following gains have typical accuracy as shown: (R2 || 20kΩ) + R1 + R3
300 12, 16 0.25 10 =
R3 R2 || 20kΩ
600 11, 12 0.25 40
700 11, 16 2 40
800 11, 12, 16 2 80

TABLE I. Internal Gain Connections. FIGURE 4. Gain Adjustment of Output Stage Using H Pad
Attenuator.
Gains other than 1, 10, 100, 200, and 500 can be set by
adding an external resistor, RG, between pin 3 and pins 12,
16, and 11. Gain accuracy is a function of RG and the Sense
internal resistors which have a ±20% tolerance with 1
20ppm/°C drift. The equation for choosing RG is shown 10 VOUT
below. ∆VIN INA110
9
3553
40k 6
RG = – 50Ω 2 RL
G –1
IL = 100mA
Gain can also be changed in the output stage by adding
resistance to the feedback loop shown in Figure 4. This is
useful for increasing the total gain or reducing the input FIGURE 5. Current Boosting the Output.
stage gain to prevent saturation of input amplifiers.
The output gain can be changed as shown in Table II. LOW BIAS CURRENT
Matching of R1 and R3 is required to maintain high CMR. R2 OF FET INPUT ELIMINATES DC ERRORS
sets the gain with no effect on CMR. Because the INA110 has FET inputs, bias currents drawn
through input source resistors have a negligible effect on DC
OUTPUT STAGE GAIN R1 AND R3 R2
accuracy. The picoamp levels produce no more than micro-
2 1.2kΩ 2.74kΩ volts through megohm sources. Thus, input filtering and
5 1kΩ 511Ω
10 1.5kΩ 340Ω input series protection are readily achievable.
TABLE II. Output Stage Gain Control. A return path for the input bias currents must always be
provided to prevent charging of stray capacitance. Other-
COMMON-MODE INPUT RANGE wise, the output can wander and saturate. A 1MΩ to 10MΩ
It is important not to exceed the input amplifiers’ dynamic resistor from the input to common will return floating
range (see Typical Performance Curves). The differential sources such as transformers, thermocouples, and
input signal and its associated common-mode voltage should AC-coupled inputs (see Applications section).
not cause the output of A1 and A2 (input amplifiers) to
exceed approximately ±10V with ±15V supplies or nonlin- DYNAMIC PERFORMANCE
ear operation will result. Such large common-mode volt- The INA110 is a fast-settling FET input instrumentation
ages, when the INA110 is in high gain, can cause saturation amplifier. Therefore, careful attention to minimize stray
of the input stage even though the differential input is very capacitance is necessary to achieve specified performance.
small. This can be avoided by reducing the input stage gain High source resistance will interact with input capacitance to
and increasing the output stage gain with an H pad attenuator reduce the overall bandwidth. Also, to maintain stability,
(see Figure 4). avoid capacitance from the output to the gain set, offset
adjust, and input pins.
OUTPUT SENSE Applications with balanced-source impedance will provide
An output sense has been provided to allow greater accuracy the best performance. In some applications, mismatched
in connecting the load. By attaching this feedback point to source impedances may be required. If the impedance in the
the load at the load site, IR drops due to load currents that
®

INA110 8
negative input exceeds that in the positive input, stray Another distinct advantage of the INA110 is the high fre-
capacitance from the output will create a net negative feed- quency CMR response. High frequency noise and sharp
back and improve the circuit stability. If the impedance in common-mode transients will be rejected. To preserve AC
the positive input is greater, the feedback due to stray CMR, be sure to minimize stray capacitance on the input
capacitance will be positive and instability may result. The lines. Matching the RCs in the two inputs will help to
degree of positive feedback depends upon source impedance maintain high AC CMR.
imbalance, operating gain, and board layout. The addition of
a small bypass capacitor of 5pF to 50pF directly between the
inputs of the IA will generally eliminate any positive feed- APPLICATIONS
back. CMR errors due to the input impedance mismatch will
also be reduced by the capacitor. In addition to general purpose uses, the INA110 is designed
to accurately handle two important and demanding applica-
The INA110 is designed for fast settling with easy gain tions: (1) inputs with high source impedances such as
selection. It has especially excellent settling in high gain. It capacitance/crystal/photodetector sensors and low-pass
can also be used in fast-settling unity-gain applications. As filters and series-input protection devices, and (2) rapid-
with all such amplifiers, the INA110 does exhibit significant scanning data acquisition systems requiring fast settling
gain peaking when set to a gain of 1. It is, however, time. Because the user has access to the output sense, current
unconditionally stable. The gain peaking can be cancelled sources can also be constructed using a minimum of external
by band-limiting the negative input to 400kHz with a simple components. Figures 6 through 19 show application circuits.
external RC circuit for applications requiring flat response.
CMR is not affected by the addition of the 400kHz RC in a
gain of 1.

+15V

1
8
X200 16 10
9 VOUT
INA110
3
6
2 7
Transducer

–15V

FIGURE 6. Transformer-Coupled Amplifier.

+15V
+15V
1
1
8
12 8
X100 10 16
9 X200 10 VOUT
INA110 VOUT 9
3 ∆VIN INA110
6 3
6
Thermocouple 2 7
2 7
Transducer or
Other Floating 1MΩ
Source –15V
–15V

100Ω
OPA121
FIGURE 7. Floating Source Instrumentation Amplifier.

Divider minimizes degredation of CMR due to

distributed capacitance on the input lines.

FIGURE 8. Instrumentation Amplifier with Shield Driver.

9 INA110
 VREF

+15V
75kΩ(1)
1
8
300Ω X500 11 10
9
1µF(1) INA110 VOUT
3
(1) 6
75kΩ
2 7

–15V

FET input allows low-pass filtering with minimal effect on DC accuracy.

NOTE: (1) Larger resistors and a smaller capacitor can be used.

FIGURE 9. Bridge Amplifier with 1Hz Low-Pass Input Filter.

+15V +15V
1µF
1 1
In 1
8 1 8
In 2 13

MPC800
12 X10 10 VOUT
10MΩ X100 10

B-B
9 9
INA110 VOUT INA110 SHC5320
3 3
100mVp-p 6 6
In 15
2 7 8 2 7
In 16
1µF
10MΩ –15V
–15V

FIGURE 12. Rapid-Scanning-Rate Data Acquisition Channel

FIGURE 10. AC-Coupled Differential Amplifier for with 5µs Settling to 0.01%.
Frequencies Greater Than 0.016Hz.

+15V

+15V 1
1 8
13 X10 13 10 VOUT
X10 8 9
12 INA110
X100 10 3
∆VIN 16 9 VOUT 6
X200 VIN 5.34MΩ(1) 5.34MΩ(1)
11 2 7
X500 6
3
2 7
1000pF
–15V
Decoder/
Latch/Driver –15V 2kΩ
2.67MΩ(1)
A0 A1 A2

NOTE: Use manual switch or low resistance relay. 500pF 500pF

Layout is critical (see section on Dynamic Performance).

NOTE: (1) For 50Hz use 3.16MΩ and 6.37MΩ.

FIGURE 11. Programmable-Gain Instrumentation Amplifier 2kΩ potentiometer sets Q.
(Precision Noninverting or Inverting Buffer with
Gain). FIGURE 13. 60Hz Input Notch Filter.

INA110 10
 +15V
+15V
R1 V1
D1 1
V1
8 +15V
D2 16
10 ∆VIN 990kΩ
X200 Overall G = 1
–15V 9
∆VIN INA110 VOUT 1
+15V 3 8
R2 6 V2 12
D3 10kΩ 10
2 7 X100 9
V2 INA110 VOUT
3
D4 6
990kΩ
–15V 2 7
–15V

10kΩ
For lower voltage, lower resistor noise: –15V
R1 = R2 = 20kΩ, D1 – D4 = FDH300 (1nA leakage)
For higher voltage, higher resistor noise:
R1 = R2 = 100kΩ, D1 – D4 = 2N4117A (1pA leakage) Common-mode range = ±1000V.
Matching of RCs on inputs will affect CMR, but CMR is dependent on ratio matching
can be optimized by trimming R1 or R2. of external input resistors.

FIGURE 14. Input-Protected Instrumentation Amplifier. FIGURE 15. High Common-Mode Voltage Differential
Amplifier.

–15V +15V
+15V
13
1
8 16
X10 13 10
6
9 7 15
∆VIN INA110 PGA102 VOUT
RG 3 8
6 2
2 7 1
4
3
–15V

CODE GAIN TYPICAL 0.01% SETTLING TIME X10 X100

00 10 6µs PGA Gain
01 100 6µs Select
10 1000 12µs

FIGURE 16. Digitally-Controlled Fast-Settling Programmable Gain Instrumentation Amplifier.

+15V
+15V
1
1 +15V 13
X10 8
13 8 12
X10 R 10
12 X100
X100 10 16 INA110 9
16 9 X200
∆VIN X200 INA110 2N2222A 11
11 X500 6
X500 6 3
3 RG 7
RG 1kΩ 2
2 7

+
–15V
–15V ∆VOUT
R
IOUT –
1
13 8
X10
RL 12 10
X100
∆VIN 16 9
X200 INA110
11
IOUT = (∆VIN) (G) (1/10k + 1/R) X500 6
3
For 0mA to 20mA output, R = 50.25Ω with (∆VIN) (G) = 1V RG 7
2

FIGURE 17. Differential Input FET Buffered Current

Source. FIGURE 18. Differential Input/Differential Output
Amplifier.
®

11 INA110