UNISONIC TECHNOLOGIES CO.

, LTD
TDA2030 LINEAR INTEGRATED CIRCUIT

14W HI-FI AUDIO AMPLIFIER

 DESCRIPTION 1

The UTC TDA2030 is a monolithic audio power amplifier TO-220-5

integrated circuit.

 FEATURES
1
* Very low external component required.
* High current output and high operating voltage. TO-220B
* Low harmonic and crossover distortion.
* Built-in Over temperature protection.
* Short circuit protection between all pins.
* Safety Operating Area for output transistors.

1
TO-220B1

 ORDERING INFORMATION
Ordering Number
Package Packing
Lead Free Halogen Free
TDA2030L-TA5-T TDA2030G-TA5-T TO-220-5 Tube
TDA2030L-TB5-T TDA2030G-TB5-T TO-220B Tube
TDA2030L-TB51-T TDA2030G-TB51-T TO-220B1 Tube

TDA2030G-TA5-T

(1) Packing Type (1) T: Tube

(2) Package Type (2) TA5: TO-220-5, TB5: TO-220B, TB51: TO-220B1
(3) Green Package (3) G: Halogen Free and Lead Free, L: Lead Free

 MARKING

UTC
TDA2030 L: Lead Free
G: Halogen Free
Lot Code Date Code
1

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TDA2030 LINEAR INTEGRATED CIRCUIT

 PIN CONFIGURATION

5 +VS
4 OUT
3 -VS
2 IN-
1 IN+

*TAB CONNECTED TO PIN 3

 PIN DESCRIPTION
PIN NO. PIN NAME FUNCTION
1 IN+ Non inverting input
2 IN- Inverting input
3 -VS -VS
4 OUT Output
5 +VS +VS

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TDA2030 LINEAR INTEGRATED CIRCUIT

 ABSOLUTE MAXIMUM RATINGS (TA=25°С, unless otherwise specified)

PARAMETER SYMBOL RATINGS UNIT
Supply Voltage Vs ±18 V
Input Voltage VIN VS V
Differential Input Voltage VI(DIFF) ±15 V
Peak Output Current(internally limited) IOUT 3.5 A
Total Power Dissipation at Tc=90C PD 20 W
Junction Temperature TJ -40 ~ +150 C
Storage Temperature TSTG -40 ~ +150 C
Note: Absolute maximum ratings are those values beyond which the device could be permanently damaged.
Absolute maximum ratings are stress ratings only and functional device operation is not implied.
 ELECTRICAL CHARACTERISTICS
(Refer to the test circuit, VS =±16V, (TA=25°С, unless otherwise specified)
PARAMETER SYMBOL TEST CONDITIONS MIN TYP MAX UNIT
Supply Voltage Vs ±6 ±18 V
Quiescent Drain Current IQ 40 60 mA
Input Bias Current II(BIAS) 0.2 2 A
Input Offset Voltage VI(OFF) Vs=±18v ±2 ±20 MV
Input Offset Current II(OFF) ±20 ±200 NA
Power Bandwidth BW POUT=12W, RL=4, GV=30dB 10 ~ 140,000 Hz
d=0.5%, Gv=30dB RL=4 12 14 W
f=40Hz to 15KHz RL=8 8 9 W
Output Power POUT
d=10%, Gv=30dB RL=4 18 W
f=1KHz RL=8 11 W
Open Loop Voltage Gain Gvo 90 dB
Closed Loop Voltage Gain Gvc f=1kHz 29.5 30 30 .5 dB
POUT=0.1 to 12W, RL=4
0.2 0.5 %
f=40Hz to 15KHz, Gv=30dB
Distortion THD
POUT=0.1 to 8W, RL=8
0.1 0.5 %
f=40Hz to 15KHz, Gv=30dB
Input Noise Voltage eN B= 22Hz to 22kHz 3 10 V
Input Noise Current iN B= 22Hz to 22kHz 80 200 pA
Input Resistance(pin 1) RIN 0.5 5 M
RL=4, Gv=30dB
Supply Voltage Rejection SVR Rg=22k, fripple=100Hz, 40 50 dB
Vripple=0.5Veff
Thermal Shut-Down Junction
TJ 145 C
Temperature

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TDA2030 LINEAR INTEGRATED CIRCUIT

 TEST CIRCUIT

+Vs

C5 C3
100 F 100nF
C1
D1
Vi 1 F
1N4001
1
5
R3
UTC 4
22k
TDA2030
2 3 C8 R4
R5
1
RL
R3 R1 D1
680 22k 1N4001

C2 C6 C4 C7
22 F 100 F 100nF 220nF

-Vs

 APPLICATION CIRCUIT

+ Vs

C5 C3
220 F 100nF
C1 D1
Vi 1 F 1N4001
1
5
R3 UTC 4
22k
TDA 2030
2 3 R4
R1 1
13k
RL
R3 D1
680 1N4001

C2 C6 C4 C7
22 F 100 F 100nF 220nF

-Vs

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TDA2030 LINEAR INTEGRATED CIRCUIT

 TYPICAL CHARACTERISTICS
Fig.2 Open loop frequency response Fig.3 Output power vs. Supply voltage
140 24
180

Phase
Gv=26dB
Phase d=0.5%
100 90 20 f=40 to 15kHz

RL=4

60 0 16

PoUT (W)
Gv(dB)

RL=8
Gain
20 12

-20 8

-60 4
1 2 3 4 5 6 7
10 10 10 10 10 10 10 24 28 32 36 40 44
Frequency (Hz) Vs (V)

Fig.4 Total harmonic distortion Fig.5 Two tone CCIF intermodulation

vs. output power distortion
2 2
10 10

1 1
10 Gv=26dB 10
d( % )

Vs=32V
d( % )

0 0 PoUT=4W
10 10 RL=4
Vs=38V
RL=8 Gv=26dB

f=15kHz Order (2f1-f2)

-1 -1
10 10
Vs=32V
RL=4 Order (2f2-f1)
f=1kHz
-2 -2
10 10
-2 -1 0 1 2 1 2 3 4 5
10 10 10 10 10 10 10 10 10 10
Po (W) Frequency (Hz)

Fig.7 Maximum allowable power

Fig.6 Large signal frequency response dissipation vs. ambient temperture
30 30
Vs=+-15V
RL=8
25 25

Vs=+-15V
20 RL=4
Vo(Vp-p)

20
PD (W)

he

he
ats 25°C

at
Rth

R t si n k
i n f vi n g
ink
=

h= h
ini

15 15 4 ° av
ha

te

he C / ing
he

ats W
/W

i
Rt nk h
ats

h= a
8 ° vi n g
in
k

C/
10 W
10

5 5
1 2 3 4 -50 0 50 100 150 200
10 10 10 10

Frequency (kHz) Ta (°C)

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TDA2030 LINEAR INTEGRATED CIRCUIT

 TYPICAL PERFORMANCE OF THE CIRCUIT OF FIG. 1

PARAMETER SYMBOL TEST CONDITIONS MIN TYP MAX UNIT
Supply Voltage VS 36 44 V
Quiescent Drain Current IQ Vs=36V 50 mA
d=0.5%,RL=4
35
f=40Hz to 15kHz,Vs=39V
d=0.5%,RL=4
28
f=40Hz to 15kHz,Vs=36V
Output Power POUT W
d=10%,f=1kHz,
44
RL=4,Vs=39V
d=10%,RL=4
35
f=1kHz,Vs=36V
Voltage Gain Gv f=1kHz 19.5 20 20.5 dB
Slew Rate SR 8 V/sec
POUT=20W,f=1kHz 0.02 %
Total Harmonic Distortion d
POUT=20W,f=40Hz to 15kHz 0.05 %
Gv=20dB,POUT=20W,
Input Sensitivity VIN 890 mV
f=1kHz,RL=4
RL=4,Rg=10k
dB
B=curve A,POUT=25W 108
Signal to Noise Ratio S/N
RL=4,Rg=10k
100
B=curve A,POUT=4W

+Vs

C5
0.22 F

R1 220 F
C3

C1 R6
56k 1.5 /40V
2.2 F
1N4001

Vi
1
5 C8
R3 2200 F
UTC 4
56k
0.22 F

TDA2030
C6

2
22 F

R2 3
C2

R8
1N4001

56k 1
RL=4

R4 R5
3.3k 30k

C4 R7 C7
10 F 1.5 0.22 F

Fig. 1 Single supply high power amplifier

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TDA2030 LINEAR INTEGRATED CIRCUIT

 TYPICAL PERFORMANCE CHARACTERISTICS

Output Power vs. Supply Voltage Total Harmonic Distortion vs. Output Power

45 Vs=36V
RL=4
Gv=20dB
10 0
PoUT (W)

35

d (%)
25
10 -1
f=15kHz
15
f=1kHz

5
40 10 -2
24 28 32 34 36 10-1 100 101
Vs (V) PoUT (W)

Output Power vs. Input Level Power Dissipation vs. Output Power

20 20
Complete
Gv=26dB
Amplifier

15 15
PoUT (W)

PD (W)

Gv=20dB
10 10

UTC
TDA2030
5 5

0 0
100 250 400 550 700 0 8 16 24 32
VIN (mV) PoUT (W)

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TDA2030 LINEAR INTEGRATED CIRCUIT

TYPICAL AMPLIFIER WITH SPLIT POWER SUPPLY

+Vs

C5 C3
100 F 100nF
C1 D1
Vi 1 F 1N4001
1
5
R3 UTC
22k
4
TDA2030
2 3 C8 R4
R5
1
RL
R3 R1 D2
680 22k 1N4001

C2 C6 C4 C7
22 F 100 F 100nF 220nF

-Vs

BRIDGE AMPLIFIER WITH SPLIT POWER SUPPLY(POUT=34W,VS=16V, VS=-16V)

Vs+

C6 C7
100 F 100nF
C1
2.2 F
1 5
IN 4
R1 UTC TDA2030
22k C8
2 0.22
3 R3 F
22k R8
1
C4
22 F
RL
R4
8
680
R7
22k

1 5
R2
4
22k UTC TDA2030
2 C9
3 0. 22F
R5
22k R9
1
Vs- C5
22 F
R6
C2 C3
680
100 F 100nF

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TDA2030 LINEAR INTEGRATED CIRCUIT
 MULTIWAY SPEAKER SYSTEMS AND ACTIVE BOXES
Multiway loudspeaker systems provide the best possible acoustic performance since each loudspeaker is
specially designed and optimized to handle a limited range of frequencies. Commonly, these loudspeaker systems
divide the audio spectrum two or three bands.
To maintain a flat frequency response over the Hi-Fi audio range the bands cobered by each loudspeaker must
overlap slightly. Imbalance between the loudspeakers produces unacceptable results therefore it is important to
ensure that each unit generates the correct amount of acoustic energy for its segments of the audio spectrum. In this
respect it is also important to know the energy distribution of the music spectrum to determine the cutoff frequencies
of the crossover filters(see Fig. 2).As an example, a 100W three-way system with crossover frequencies of 400Hz
and 3KHz would require 50W for the woofer,35W for the midrange unit and 15W for the tweeter.
Both active and passive filters can be used for crossovers but active filters cost significantly less than a good
passive filter using aircored inductors and non-electrolytic capacitors. In addition active filters do not suffer from the
typical defects of passive filters:
--Power less;
--Increased impedance seen by the loudspeaker(lower damping)
--Difficulty of precise design due to variable loudspeaker impedance.
Obviously, active crossovers can only be used if a power amplifier is provide for each drive unit. This makes it
particularly interesting and economically sound to use monolithic power amplifiers.
In some applications complex filters are not relay necessary and simple RC low-pass and high-pass
networks(6dB/octave) can be recommended.
The result obtained are excellent because this is the best type of audio filter and the only one free from phase and
transient distortion.
The rather poor out of band attenuation of single RC filters means that the loudspeaker must operate linearly well
beyond the crossover frequency to avoid distortion.
A more effective solution is shown in Fig. 3.
The proposed circuit can realize combined power amplifiers and 12dB/octave or high-pass or low-pass filters.
In proactive, at the input pins amplifier two equal and in-phase voltages are available, as required for the active
filter operations.
The impedance at the Pin(-) is of the order of 100,while that of the Pin (+) is very high, which is also what was
wanted.

Fig. 2 Power distribution vs. frequency

100 Fig. 3 Active power filter

IEC/DIN NOISE
Vs+
80 C1 C2 C3
SPECTRUM Morden
FOR SPEAKER Music
TESTING Spectrum RL
60
R1 R2 R3
3.3k
40 Vs-

20 100

0
101 10 2 103 10 4 10 5

The components values calculated for fc=900Hz using a Bessel 3rd Sallen and Key structure are:
C1=C2=C3=22nF,R1=8.2K,R2=5.6K,R3=33K.
Using this type of crossover filter, a complete 3-way 60W active loudspeaker system is shown in Fig. 20.
It employs 2nd order Buttherworth filter with the crossover frequencies equal to 300Hz and 3kHz.
The midrange section consistors of two filters a high pass circuit followed by a low pass network. With Vs=36V the
output power delivered to the woofer is 25W at d=0.06%( 30W at d=0.5%).The power delivered to the midrange and
the tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and impedance
(RL=4 to 8).
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TDA2030 LINEAR INTEGRATED CIRCUIT
It is quite common that midrange and tweeter speakers have an efficiency 3dB higher than woofers.

Vs+

Low-pass 2200 F 0.22 F 1N4001

1.5
300Hz
IN 1 F 22k 22k
1 5 BD908

18nF
UTC 4
680 TDA2030
2200 F
2 0.22 F
33nF 3
22k 100 F 1

BD907 4
1.5
100 1N4001 0.22 F
3.3k

Woofer

Vs+
Band-pass 0.22 F
300Hz to 3KHz
1N4001

0.1 F 0.1 F 22k 22k

1 5
220 F
18nF
UTC 4
3.3k
TDA2030
6.8k
2 1
3.3nF
3 8

0.22 F
1N4001

100 F
2.2k Midrange

100 Vs+
0.22 F
High-pass
3KHz 1N4001
Vs+
3.3 nF 3.3 nF
1 5
100 F
UTC 4
22k
12k 22k TDA2030
2 1
3 8
1N4001
0.22F
22k
100 F

47 F
2.2k
Tweeter
High-pass
100
3KHz

 MUSICAL INSTRUMENTS AMPLIFIERS

Another important field of application for active system is music.
In this area the use of several medium power amplifiers is more convenient than a single high power amplifier, and
it is also more reliable. A typical example (see Fig. 4) consist of four amplifiers each driving a low-cost, 12 inch
loudspeaker. This application can supply 80 to 160W rms.

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TDA2030 LINEAR INTEGRATED CIRCUIT

 TRANSIENT INTER-MODULATION DISTORTION (TIM)

Transient inter-modulation distortion is an unfortunate phenomena associated with negative-feedback amplifiers.
When a feedback amplifier receives an input signal which rises very steeply, i.e. contains high-frequency
components, the feedback can arrive too late so that the amplifiers overloads and a burst of inter-modulation
distortion will be produced as in Fig.5. Since transients occur frequently in music this obviously a problem for the
designed of audio amplifiers. Unfortunately, heavy negative feedback is frequency used to reduce the total harmonic
distortion of an amplifier, which tends to aggravate the transient inter-modulation (TIM situation.)

Fig.4 High power active box for musical instrument Fig.5 Overshoot phenomenon in feedback amplifiers

FEEDBACK
20 to 40W PATH
Amplifier
¦Â V4

INPUT POWER OUTPUT

PRE AMPLIFIER
V1 V2 V3 AMPLIFIER V4
20 to 40W
Amplifier

V1

20 to 40W V2
Amplifier

20 to 40W
Amplifier V3

V4

The best known method for the measurement of TIM consists of feeding sine waves superimposed onto square
wavers, into the amplifier under test. The output spectrum is then examined using a spectrum analyzer and
compared to the input. This method suffers from serious disadvantages: the accuracy is limited, the measurement is
a tatter delicate operation and an expensive spectrum analyzer is essential.
The "inverting-sawtooth" method of measurement is based on the response of an amplifier to a 20KHz saw-tooth
wave-form. The amplifier has no difficulty following the slow ramp but it cannot follow the fast edge. The output will
follow the upper line in Fig.6 cutting of the shade area and thus increasing the mean level. If this output signal is
filtered to remove the saw-tooth, direct voltage remains which indicates the amount of TIM distortion, although it is
difficult to measure because it is indistinguishable from the DC offset of the amplifier. This problem is neatly avoided
in the IS-TIM method by periodically inverting the saw-tooth wave-form at a low audio frequency as shown in
Fig.7. In the case of the saw-tooth in Fig. 8 the mean level was increased by the TIM distortion, for a saw-tooth in the
other direction the opposite is true.

SR(V/s) Input
Signal
m2
m1
Filtered
Output
Siganal

Fig.6 20kHz sawtooth waveform Fig.7 Inverting sawtooth waveform

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TDA2030 LINEAR INTEGRATED CIRCUIT
 TRANSIENT INTER-MODULATION DISTORTION (TIM) (Cont.)

The result is an AC signal at the output whole peak-to-peak value is the TIM voltage, which can be measured
easily with an oscilloscope. If the peak-topeak value of the signal and the peak-to-peak of the inverting sawtooth are
measured, the TIM can be found very simply from:
VOUT
TIM  * 100
Vsawtooth

Fig. 8 TIM distortion Vs. Output Power Fig. 9 TIM design diagram(fc=30kHz)
101 102

UTC2030A RC Filter fc=30kHz

BD908/907
Gv=20dB
Vs=36V
100 101
RL=4

SR(V/¦Ìs)
TIM(%)

1%
.0
=0

%
.1
M
10-1 RC Filter fc=30kHz 100

=0
TI

%
TI

=1
M
TI
10-2 10-1
10-1 100 101 10 2 10-1 100 10 1 102
PoUT(W) Vo(Vp-p)

In Fig.8 The experimental results are shown for the 30W amplifier using the UTC TDA2030 as a driver and a
low-cost complementary pair. A simple RC filter on the input of the amplifier to limit the maximum signal slope(SS) is
an effective way to reduce TIM.
The Diagram of Fig.9 can be used to find the Slew-Rate(SR) required for a given output power or voltage and a
TIM design target.
For example if an anti-TIM filter with a cutoff at 30kHz is used and the max. peak to peak output voltage is 20V
then, referring to the diagram, a Slew-Rate of 6V/s is necessary for 0.1% TIM.
As shown Slew-Rates of above 10V/s do not contribute to a further reduction in TIM.
Slew-Rates of 100V/s are not only useless but also a disadvantage in hi-fi audio amplifiers because they tend to
turn the amplifier into a radio receiver.

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TDA2030 LINEAR INTEGRATED CIRCUIT

 POWER SUPPLY
Using monolithic audio amplifier with non regulated supply correctly. In any working case it must provide a supply
voltage less than the maximum value fixed by the IC breakdown voltage.
It is essential to take into account all the working conditions, in particular mains fluctuations and supply voltage
variations with and without load. The UTC TDA2030 (Vsmax=44V) is particularly suitable for substitution of the
standard IC power amplifiers (with Vsmax=36V) for more reliable applications.
An example, using a simple full-wave rectifier followed by a capacitor filter, is shown in the table and in the diagram
of Fig.10.
A regulated supply is not usually used for the power output stages because of its dimensioning must be done
taking into account the power to supply in signal peaks. They are not only a small percentage of the total music
signal, with consequently large overdimensioning of the circuit.
Even if with a regulated supply higher output power can be obtained(Vs is constant in all working conditions),the
additional cost and power dissipation do not usually justify its use. using non-regulated supplies, there are fewer
designee restriction. In fact, when signal peaks are present, the capacitor filter acts as a flywheel supplying the
required energy.
In average conditions, the continuous power supplied is lower. The music power/continuous power ratio is greater
in case than for the case of regulated supplied, with space saving and cost reduction.

Fig.10 DC characteristics of 50W non-regulated supply

36
Ripple (Vp-p)

34
VOUT(V)

Ripple
4 220V
32
Vo
2
30 3300 F

Vout 0
28

0 0.4 0.8 1.2 1.6 2.0

IOUT(A)

DC Output Voltage(VOUT)
Mains(220V) Secondary Voltage
IOUT =0 IOUT =0.1A IOUT =1A
+20% 28.8V 43.2V 42V 37.5V
+15% 27.6V 41.4V 40.3V 35.8V
+10% 26.4V 39.6V 38.5V 34.2V
— 24V 36.2V 35V 31V
-10% 21.6V 32.4V 31.5V 27.8V
-15% 20.4V 30.6V 29.8V 26V
-20% 19.2V 28.8V 28V 24.3V

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TDA2030 LINEAR INTEGRATED CIRCUIT

 SHORT CIRCUIT PROTECTION

The UTC TDA2030 has an original circuit which limits the current of the output transistors. This function can be
considered as being peak power limiting rather than simple current limiting. It reduces the possibility that the device
gets damaged during an accidental short circuit from AC output to Ground.
 THERMAL SHUT-DOWN
The presence of a thermal limiting circuit offers the following advantages:
1).An overload on the output (even if it is permanent),or an above limit ambient temperature can be easily
supported since the Tj can not be higher than 150C
2).The heatsink can have a smaller factor of safety compared with that of a congenital circuit, There is no
possibility of device damage due to high junction temperature increase up to 150C, the thermal shut-down
simply reduces the power dissipation and the current consumption.
 APPLICATION SUGGESTION
The recommended values of the components are those shown on application circuit of Fig.14. Different values can
be used. The following table can help the designer.
SMALLER THAN
RECOMMENDED LARGER THAN
COMPONENT PURPOSE RECOMMENDED
VALUE RECOMMENDED VALUE
VALUE
Closed loop gaon
R1 22K Increase of Gain Decrease of Gain
setting.
Closed loop gaon
R2 680 Decrease of Gain Increase of Gain
setting.
Non inverting input Decrease of input
R3 22K Increase of input impedance
biasing impedance
Danger of oscillation at high
R4 1 Frequency stability frequencies with inductive
loads.
Poor high frequencies
R5 3R2 Upper frequency cutoff Danger of oscillation
attenuation
Increase of low
C1 1F Input DC decoupling
frequencies cutoff
Inverting DC Increase of low
C2 22F
decoupling frequencies cutoff
C3,C4 0.1F Supply voltage bypass Danger of oscillation
C5,C6 100F Supply voltage bypass Danger of oscillation
C7 0.22F Frequency stability Larger bandwidth
C8 1/(2*B*R1) Upper frequency cutoff smaller bandwidth Larger bandwidth
To protect the device
D1,D2 1N4001 against output voltage
spikes.

UTC assumes no responsibility for equipment failures that result from using products at values that
exceed, even momentarily, rated values (such as maximum ratings, operating condition ranges, or other
parameters) listed in products specifications of any and all UTC products described or contained herein .
UTC products are not designed for use in life support appliances, devices or systems where malfunction
of these products can be reasonably expected to result in personal injury. Reproduction in whole or in
part is prohibited without the prior written consent of the copyright owner. UTC reserves the right to
make changes to information published in this document, including without limitation specifications and
product descriptions, at any time and without notice. This document supersedes and replaces all
information supplied prior to the publication hereof.

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