IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. 67, NO.

6, JUNE 2019 3869

Rectangular Grating Waveguide Slot Array Antenna

for SATCOM Applications
Weile Yuan , Xianling Liang , Senior Member, IEEE, Lina Zhang, Junping Geng , Senior Member, IEEE,
Weiren Zhu , Senior Member, IEEE, and Ronghong Jin, Fellow, IEEE

Abstract— This paper introduces a rectangular grating is to connect microwave filters to the receiving antennas.
waveguide slot array antenna that provides a method for the However, filters with high rejection or the cascade of multiple
design of satellite communication (SATCOM) receiving antennas. filters generally introduce additional insertion loss and space to
By integrating the radiating slots with a rectangular grating
waveguide, which functions as a frequency-selective transmis- the system. Therefore, the filtering antennas, which simultane-
sion line, the antenna realizes an extra filtering response. The ously possess the filtering responses and radiation abilities, are
operation bandwidth and out-of-band rejection of the antenna good candidates to be applied in miniature SATCOM system
can be tuned by adjusting the rectangular grating waveguide to enhance the isolation between the receiving and transmitting
parameters. In order to verify the proposed design concept, antennas, reduce the number of external cascaded filters, and
a prototype K u-band eight-slot rectangular grating waveguide
slot array antenna is designed, fabricated, and measured, and its ease the difficulty of the anti-interference design.
performance is compared with that of the conventional eight-slot Various research studies on the filtering antennas were
rectangular waveguide slot array antenna. The results show that published for different applications [3]–[15], most of which
the proposed antenna works well in the receiving frequencies of were based on the printed circuit structure. In [3]–[12], dif-
12.25–12.75 GHz and suppresses the realized gains with addi- ferent types of antennas with extra filtering responses were
tional measured 14.8–21.3 dB in the transmitting frequencies
of 14.0–14.5 GHz, which confirms its extra filtering response. designed, including microstrip patch filtering antennas [3], [4],
Simultaneously, the measured antenna efficiency of the proposed -shaped printed filtering antennas [5], [6], substrate inte-
antenna (68.3%–88.8%) is similar to that of the conventional grated waveguide slot filtering antennas [7], [8], filtering patch
antenna (66.9%–84.6%). antennas integrated with multimode filters [9], [10], filtering
Index Terms— Filtering antenna, rectangular grating patch arrays fed with filtering networks [11], [12], and so
waveguide, satellite communication (SATCOM), slot array on. They utilized the codesigned method of replacing the
antenna. last stages of the filters with the antennas to save space.
However, these designs contained extra filtering circuits, which
I. I NTRODUCTION limited their compactness and introduced extra insertion loss

T ODAY, satellite communication (SATCOM) system

is widely used in military and commercial applica-
tions [1], [2]. In the future, its miniaturization will become
to the antennas. Recently, new approaches that merged the
antennas and the filtering structures together were proposed
in [13]–[15]. In [13], a parasitic loop was added to the
a hot topic for the implementation in small platforms, such radiating patch to improve the antenna’s high-frequency selec-
as airplanes, ships, and vehicles. One important feature of the tivity. In [14], a U-shaped slot and three shorting pins were
miniature SATCOM system is the reduction in the spacing introduced to the stack patch antenna to achieve a filtering
between the receiving and transmitting antennas or even their response with a compact design. In [15], the U-shaped patches
aperture-shared design. In such situations, the receiving chan- and the multistub feed line were merged compactly, which also
nel will suffer from the high-powered signals of the transmit- realized an extra filtering response. The antenna dimensions
ting antennas, which make the first-stage low noise amplifier and loss were further saved in these designs. However, these
saturate and fail to work. An effective solution to this problem antennas still have their drawbacks for miniature SATCOM
applications. For one thing, since these antenna elements are
Manuscript received December 19, 2018; revised February 28, 2019;
accepted March 3, 2019. Date of publication March 21, 2019; date of current generally attached with extra filtering structures, the coupling
version May 31, 2019. This work was supported by the National Natural effects from elements to elements become more severe in the
Science Foundation of China under Grant 61671416, Grant 61571298, and antenna array design. This instead increases the design diffi-
Grant 61571289. (Corresponding author: Xianling Liang.)
W. Yuan, X. Liang, J. Geng, W. Zhu, and R. Jin are with the Department culty of the antenna array. For another thing, the feed network
of Electronics Engineering, School of Electrical, Information and Electronics design becomes more complicated due to the existence of the
Engineering, Shanghai Jiao Tong University, Shanghai 200240, China (e-mail: filtering structures, especially for the antenna arrays.
liangxl@sjtu.edu.cn).
L. Zhang is with the Department of Antenna, Shanghai Aerospace Waveguide slot array antenna is suitable for SAT-
Electronic Technology Institute, Shanghai 201109, China (e-mail: COM applications due to its high efficiency, pure polar-
lnzhang0914@163.com). ization, and high mechanical strength. Many waveguide
Color versions of one or more of the figures in this paper are available
online at http://ieeexplore.ieee.org. slot array antennas were proposed for different applica-
Digital Object Identifier 10.1109/TAP.2019.2905784 tions [16]–[24]. In [16]–[20], the presented antennas showed

0018-926X © 2019 IEEE. Personal use is permitted, but republication/redistribution requires IEEE permission.
See http://www.ieee.org/publications_standards/publications/rights/index.html for more information.

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 3870 IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. 67, NO. 6, JUNE 2019

good performances in their working frequencies, but they

did not include extra filtering designs. In [21], T-shaped
bandpass filters and bandstop filters were integrated into the
feed network of the E-band waveguide slot array antenna,
which achieved an extra filtering response. In [22], two
evanescent-mode ridged waveguide filters are integrated into
the two-way waveguide divider to obtain a filtering response.
In [23] and [24], diplexers were also connected to the anten-
nas’ feed networks, which realized a channel selecting func-
tion in E-band and K a-band, respectively. Still, the filtering
structures in [21]–[24] were integrated into the antenna feed
networks. Since the waveguide slot array antenna naturally
owns a large interior, a more compact filtering integration into
the antenna itself is available.
In this paper, a rectangular grating waveguide slot array
antenna with an extra filtering response is proposed to provide
a method for the design of SATCOM receiving antennas.
Instead of using a normal rectangular waveguide, the antenna
utilizes a rectangular grating waveguide, which acts as a
frequency-selective waveguide transmission line, to achieve Fig. 1. Configurations of the rectangular grating waveguide slot array antenna
the filtering performance. To verify the design concept, and the rectangular grating waveguide.
we choose the antenna design in the K u-band SATCOM sys-
tem, where the receiving antennas operate in 12.25–12.75 GHz
and the signals from the high-powered transmitting antennas
are in 14.0–14.5 GHz, which are harmful to the receiving
channel and can be suppressed by the receiving antennas.
A prototype K u-band eight-slot rectangular grating waveguide
slot array antenna is designed, fabricated, and measured, and
it is compared with the conventional eight-slot rectangular
waveguide slot array antenna. The results show that the
proposed antenna not only operates well in the receiving fre-
quencies of 12.25–12.75 GHz but also suppresses the realized
gains in the transmitting frequencies of 14.0–14.5 GHz much
better than the conventional antenna does, which confirms
its extra filtering response. Moreover, the proposed antenna
shows a similar antenna efficiency compared with that of Fig. 2. Calculated dispersion diagram of the rectangular grating waveguide
the conventional antenna, which indicates that almost no (parameters are: a = 19.05 mm, b = 9.525 mm, h g = 3.7 mm, dg = 9.7 mm,
additional efficiency loss is introduced. and tg = 0.5 mm).

II. A NTENNA C ONFIGURATION , M ECHANISM , A. Analysis of Rectangular Grating Waveguide

AND D ESIGN
The rectangular grating waveguide contributes to the
Fig. 1 shows the configuration of the rectangular grating antenna’s extra frequency selectivity, and its characteristics
waveguide slot array antenna. The antenna contains multiple are analyzed by the dispersion diagram, as shown in Fig. 2.
metallic sheets on its bottom broad wall. These metallic sheets It is observed that there exist multiple dispersion curves in the
are of the same dimension and are distributed uniformly. diagram. These curves correspond to different transmission
A number of longitudinal slots are etched on the antenna’s modes in the rectangular grating waveguide, including TEx10
top broad wall for radiation. They are arranged in the same mode (the fundamental mode), TEx20 mode, and TEx11 mode
manner as that of the conventional rectangular waveguide slot (the higher order modes). Other higher order modes are
array antennas. The spacing between adjacent slots is equal neglected. When a signal is within the frequency range of
to half a waveguide wavelength of the rectangular grating one of these transmission modes, for instance, the range of
waveguide. As shown in Fig. 1, it is noted that the rectangular TEx10 mode, it can propagate along the waveguide smoothly
grating waveguide is a classic slow wave structure [25]–[30], since there are certain propagation constants β. However, if a
which has a shorter waveguide wavelength than that of the signal is located in the “frequency gaps” between adjacent
conventional rectangular waveguide. Ideally, it is a periodic modes, for example, the gap between TEx10 mode and TEx20
structure whose waveguide inner size is a × b, periodic mode, it will experience a high attenuation and, thus, blocked
metallic sheet size is a × h g × tg , and metallic sheet spacing by the waveguide. In this manner, the rectangular grating
is dg . waveguide performs a bandstop response. Here, we define the

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 YUAN et al.: RECTANGULAR GRATING WAVEGUIDE SLOT ARRAY ANTENNA FOR SATCOM APPLICATIONS 3871

Fig. 3. Calculated passband and stopband distributions affected by different metallic sheet parameters. (a) Height h g (dg = 9.7 mm and tg = 0.5 mm).
(b) Spacing dg (h g = 3.7 mm and tg = 0.5 mm). (c) Thickness tg (h g = 3.7 mm and dg = 9.7 mm).

Fig. 4. Calculated propagation constant β in passband affected by different metallic sheet parameters. (a) Height h g (dg = 9.7 mm and tg = 0.5 mm).
(b) Spacing dg (h g = 3.7 mm and tg = 0.5 mm). (c) Thickness tg (h g = 3.7 mm and dg = 9.7 mm).

frequency range of TEx10 mode ( f a , f b ) as the passband, and that β is also affected by the parameters, especially for h g .
the “frequency gap” between the TEx10 mode and TEx20 mode At 12.5 GHz, when h g increases from 3.1 to 4.3 mm, β is evi-
( f b , f c ) as the stopband. dently enhanced from 231.25 to 274.00 rad/m. On the contrary,
We follow the eigenmode method presented in [30] to more the other two parameters have less effects on β. Moreover, the
detailedly study the characteristics of the rectangular grating attenuation constant α in stopband shows the bandstop ability
waveguide. MATLAB software is used to build a mathematical of the rectangular grating waveguide, and the results are shown
model for calculation. For a better applicability, the waveguide in Fig. 5, where 14.0, 14.25, and 14.5 GHz within the stopband
inner size is selected as a × b = 19.05 mm × 9.525 mm are sampled. Also, α is effectively enhanced by the increase
(WR-75). Other nonstandard dimensions are also available as in h g , and it is influenced by dg when dg is relatively small.
long as b/a is not too large to eliminate the stopband [27]. The results of the calculations show that the passband and
The calculating results are shown in Figs. 3–5. Here, three stopband distribution characteristic of the rectangular grating
rectangular grating waveguide parameters are variable, includ- waveguide is mainly related to the metallic sheet height h g
ing the metallic sheet height h g , spacing dg , and thickness tg . and spacing dg . In addition, the propagation constants β in
The passband and stopband distributions are shown in Fig. 3, passband and the attenuation constants α in stopband are also
and f a , fb , and f c represent the three frequency limits of the affected by different metallic sheet parameters, especially for
passband and the stopband, as marked in Fig. 2. As can be h g . These characteristics can be tuned to meet the antenna
observed, the values of f a and f c are relatively stable with design requirements. Moreover, considering that tg is less
the changes of three parameters. By contrast, the value of f b affected on the rectangular grating waveguide characteristics,
is apparently affected by the adjustments of h g and dg . When it is usually selected as thin as possible according to the
h g increases from 3.1 to 4.3 mm, f b decreases from 14.33 process conditions.
to 12.89 GHz; and when dg increases from 8.2 to 11.2 mm, The simulated inner upper surface current distributions of
f b decreases from 14.46 to 12.79 GHz. It is indicated that the rectangular grating waveguide are exhibited in Fig. 6. Two
the passband and stopband distributions can be tuned by frequencies of 12.5 and 14.25 GHz, which are, respectively,
adjusting h g and dg independently. In addition, the propagation within the passband and stopband, are investigated. As can be
constant β in passband reflects the waveguide wavelength of observed, at 12.5 GHz, the currents are fully distributed on the
the rectangular grating waveguide, and the calculating results rectangular grating waveguide’s inner upper surface. Along the
are shown in Fig. 4. Here, three frequencies of 12.25, 12.5, waveguide, the current vectors are distributed periodically and
and 12.75 GHz within the passband are studied. It is seen they alternately point at outward and inward directions with

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 3872 IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. 67, NO. 6, JUNE 2019

Fig. 5. Calculated attenuation constant α in stopband affected by different metallic sheet parameters. (a) Height h g (dg = 9.7 mm and tg = 0.5 mm).
(b) Spacing dg (h g = 3.7 mm and tg = 0.5 mm). (c) Thickness tg (h g = 3.7 mm and dg = 9.7 mm).

Fig. 7. Configuration of the prototype K u-band eight-slot rectangular grating

waveguide slot array antenna.

Fig. 6. Simulated inner upper surface current distributions of the rectangular

grating waveguide at (a) 12.5 GHz and (b) 14.25 GHz.

respect to the central axis, which makes the waveguide suitable

for longitudinal radiating slots etching. On the other hand,
at 14.25 GHz, the currents are only strong near the input port
but encounter a high attenuation along the waveguide. In this
case, the currents are quite weak for the slots to radiate, which
will result in a low radiation energy.

Fig. 8. Simulated reflection coefficients of four antennas designed on different

B. Analysis of Antenna Bandwidth and Out-of-Band rectangular grating waveguides.
Rejection
As analyzed in Section II-A, the passband and stopband
distributions of the rectangular grating waveguide are tuned by Table I. Four waveguides perform the similar passband and
adjusting h g and dg independently. Under the same passband stopband distributions, which are around 7.87–13.57 GHz and
and stopband design requirement, there may exist diverse h g 13.57–15.75 GHz. Although their propagation constants β in
and dg combinations that are appropriate for the filtering passband and attenuation constants α in stopband are different.
antenna design. For the investigation, we select four rec- As listed in Table I, their β at 12.5 GHz and α at 14.25 GHz,
tangular grating waveguides with different h g and dg (other which are denoted by β12.5GHz and α14.25 GHz , respectively,
parameters are the same) to design the antennas, as listed in are different.

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 YUAN et al.: RECTANGULAR GRATING WAVEGUIDE SLOT ARRAY ANTENNA FOR SATCOM APPLICATIONS 3873

TABLE I
C HARACTERISTICS OF F OUR D IFFERENT R ECTANGULAR G RATING WAVEGUIDES AND D ESIGNED A NTENNAS

Fig. 10. Calculated normalized waveguide wavelengths of four different

rectangular grating waveguides.

Fig. 9. Simulated normalized radiation patterns in H-plane at 12.5 GHz of

four antennas designed on different rectangular grating waveguides.
this phenomenon, the waveguide wavelengths of the four
rectangular grating waveguides are calculated by MATLAB.
Utilizing these rectangular grating waveguides, four proto- As shown in Fig. 10, these wavelengths are normalized by
type K u-band eight-slot rectangular grating waveguide slot their respective wavelengths at 12.5 GHz, which are related
array antennas are designed, and the configuration of the to the antenna lengths. It is observed that the four rectangular
prototype antenna is shown in Fig. 7. The slot array composes grating waveguides have the different normalized waveguide
of eight slots in total of the same dimensions (ls , ws , ds , and wavelength variation rates in 12.5–13.0 GHz. Among them,
rs ) to achieve a good uniform excitation. Their spacing is the one with h g = 4.1 mm and dg = 8.8 mm shows the
ps , which is equal to half a rectangular grating waveguide sharpest wavelength variation. This implies that at higher
wavelength at 12.5 GHz λg,12.5 GHz /2. A short matching frequencies, the input electromagnetic (EM) wave into the
section is applied to improve the matching performance. It is corresponding antenna suffers from the most severe mismatch
ps /2 (or λg,12.5 GHz /4) long and contains a single metallic to the radiating slots, which causes the poorest resonance of
sheet with a height h g2 . The simulations are carried out by the slot array antenna. Thus, its higher frequency limit in
HFSS 15. operation band is most reduced. Empirically, at the frequencies
The simulated reflection coefficients and normalized radi- that are near the stopband, a larger propagation constant
ation patterns of four prototype antennas are compared in β12.5 GHz usually causes a sharper normalized waveguide
Figs. 8 and 9, respectively. In the receiving frequencies, wavelength variation. Therefore, a larger β12.5 GHz generally
four antennas show good reflection coefficients and achieve corresponds to a narrower operation bandwidth, as listed
good broadside radiation patterns at 12.5 GHz. However, their in Table I.
operation bandwidths are different, especially for the higher On the other hand, in the transmitting frequencies, the
frequency limit. For the antenna with h g = 3.5 mm and simulated realized gains of the antennas are also different.
dg = 10.1 mm, the −15 dB bandwidth is 12.04–12.89 GHz; As shown in Fig. 11, the antenna with h g = 4.1 mm and
and for the antenna with h g = 4.1 mm and dg = 8.8 mm, the dg = 8.8 mm performs the lowest realized gains of −20.32
−15 dB bandwidth is reduced to 12.05–12.74 GHz. To explain to −24.87 dBi, whereas the antenna with h g = 3.5 mm and

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 3874 IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. 67, NO. 6, JUNE 2019

Fig. 11. Simulated out-of-band realized gains of four antennas designed on

different rectangular grating waveguides. Fig. 12. Simulated normalized radiation patterns in H-plane at 12.5 GHz of
the prototype antenna of different slot spacings ps .

dg = 10.1 mm performs the highest realized gains of −10.46

to −17.53 dBi, which implies the worst out-of-band rejection. which indicates a good broadside radiation performance. Then,
This is because the rectangular grating waveguide with h g = the waveguide wavelength is estimated to be λg,12.5 GHz =
4.1 mm and dg = 8.8 mm provides the largest attenuation 2× ps = 25.9 mm, and the propagation constant is β12.5 GHz =
constant α in stopband, as listed in Table I. This represents the 242.59 rad/m. This estimated β12.5 GHz is quite close to the
highest energy attenuation rate along the rectangular grating result of β12.5 GHz = 247.12 rad/m calculated in Fig. 4.
waveguide in stopband, which results in the smallest radiation The error may be caused by the antenna’s finite length and the
energy of the corresponding antenna. Thus, the realized gains coupling effects between the radiating slots and the metallic
are most suppressed. sheets.
In the investigation, it is concluded that among the four Then, the slot offset ds and length ls are optimized for a
antennas, the one with a wider operation bandwidth usually better slot resonance. The input impedances (Z in) of different
performs a weaker out-of-band rejection. Therefore, under the ds and ls are shown in Fig. 13. It is seen that among various
similar passband and stopband distributions, the antenna oper- parameter combinations, the combination of ds = 3.1 mm
ation bandwidth and out-of-band rejection can compromise and ls = 12 mm makes the flat input resistance and reactance
with each other by adjusting parameters h g and dg to better curves within the receiving frequencies. This means a good
meet the antenna design requirements. slot resonance in operation band. Other ds and ls combinations
cause more fluctuated impedance curves, which indicates a
poor slot resonance.
C. Antenna Design Guideline In addition, the distance d1 between the innermost metallic
Based on the prototype antenna shown in Fig. 7, the antenna sheet and the short wall determines the relative position
design guideline is illustrated as follows. between all the metallic sheets and the radiating slots. The
1) Rectangular Grating Waveguide Selection: An appropri- change of d1 influences the input reactance but has small
ate rectangular grating waveguide is selected for the antenna effects on the input resistance and radiation pattern of the
design. The parameters are a = 19.05 mm, b = 9.525 mm, antenna. As shown in Fig. 14, it is optimized to be 5 mm
h g = 3.7 mm, dg = 9.7 mm, and tg = 0.5 mm. Its dispersion for a good input reactance.
graph is shown in Fig. 2. As can be observed, the passband and 3) Impedance Matching Design: The matching section is
the stopband of the rectangular grating waveguide are 7.87– applied and adjusted for a better matching performance. Its
13.57 GHz and 13.57–15.75 GHz, respectively, which fully effects are shown in Figs. 15 and 16. In the receiving fre-
cover the receiving frequencies of 12.25–12.75 GHz and the quencies, the input resistance of the antenna with the matching
transmitting frequencies of 14.0–14.5 GHz. section is larger than that of the antenna without the matching
2) Slot Parameters Analysis and Optimization: The radiat- section. Its input resistance is enhanced to be closer to the
ing slot parameters are analyzed and optimized for a good input port characteristic impedance Z 0 . Meanwhile, the input
radiation performance. Here, the slot width is selected to be reactances of the antennas with and without the matching
ws = 1.2 mm (equal to λ0,12.5 GHz /20, λ0,12.5 GHz is the section are both close to 0 . Hence, the antenna with
wavelength in free space at 12.5 GHz) to ensure an effective the matching section performs the lower reflection coeffi-
E-field excitation [31]. The slot spacing ps is required to be cients in the receiving frequencies, as shown in Fig. 16. The
λg,12.5 GHz /2 to realize a uniform excitation. The normalized function of the matching section can be understood by a
radiation patterns of different slot spacings ps are shown in quarter-wavelength impedance converter. Assume the input
Fig. 12. It is seen that among different ps values, ps = 12.95 impedances of the slot array with and without the match-
mm provides a radiation main beam pointing at almost 0◦ , ing section are Z in and Z in0 , respectively, and the effective

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 YUAN et al.: RECTANGULAR GRATING WAVEGUIDE SLOT ARRAY ANTENNA FOR SATCOM APPLICATIONS 3875

Fig. 15. Simulated input impedances of the prototype antenna with and
without the matching section. (a) Resistance. (b) Reactance.
Fig. 13. Simulated input impedances of the prototype antenna of different
slot offsets ds and lengths ls . (a) Resistance. (b) Reactance.

Fig. 16. Simulated reflection coefficients of the prototype antenna with and
without the matching section.

Fig. 14. Simulated input reactances of the prototype antenna of different approximated by
distances d1 .

Z 12
Z in = . (1)
Z in0
characteristic impedance of the matching section is  Z 1 (here, If the condition of

Z 1 is an effective parameter because the short matching section
is not a uniform transmission line), their relation can be Z in0 < 
Z1 < Z0 (2)

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 3876 IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. 67, NO. 6, JUNE 2019

TABLE II
D IMENSION OF THE P ROTOTYPE K u-BAND E IGHT-S LOT R ECTANGULAR
G RATING WAVEGUIDE S LOT A RRAY A NTENNA

TABLE III
D IMENSION OF THE R EFERENTIAL K u-BAND E IGHT-S LOT C ONVEN -
TIONAL R ECTANGULAR WAVEGUIDE S LOT A RRAY A NTENNA

is satisfied, the converted Z in will be larger than the original

Z in0 and becomes closer to Z 0 , which consequently improves
the antenna matching performance.
The matching performance is further optimized by adjusting
the metallic sheet height h g2 . As shown in Fig. 15, when
h g2 decreases from 3.7 mm (equal to h g ) to 3.3 mm, the Fig. 17. Fabricated antennas. (a) Top views of two antennas. (b) Side view
antenna’s input resistance is further enhanced and closer to Z 0 . of the proposed antenna. (c) Side view of the conventional antenna.
Meanwhile, the input reactance remains stable. Thus, as shown
in Fig. 16, the reflection coefficients are further optimized in
the receiving frequencies. This can be explained as that the
decrease in h g2 leads to the enhancement of the matching
section’s effective characteristic impedance  Z 1 . As expressed
in (1), when  Z 1 is enhanced, the value of Z in is also enhanced,
and the reflection coefficients are optimized. Nevertheless,
there is another consideration on the h g2 selection, that the
decrease in h g2 also weakens the out-of-band rejection of
the antenna. This is because the matching section itself also
functions as a signal rejecter in the stopband, and its attenua-
tion constant α is reduced by the decrease in h g2 . Therefore,
we select h g2 = 3.5 mm in the design, which ensures
that the reflection coefficients are lower than −15 dB in
12.25–12.75 GHz.
Fig. 18. Simulated and measured reflection coefficients of the proposed and
The overall design parameters of the antenna are listed in conventional antennas.
Table II.

III. R ESULTS AND D ISCUSSION reference antenna is also designed, fabricated, and measured.
The prototype K u-band eight-slot rectangular grating Its structural parameters are included in Fig. 7 (except for the
waveguide slot array antenna designed in Section II-C is metallic sheets) and the values are listed in Table III. The
fabricated and measured for demonstration. It is made of photographs of both antennas are shown in Fig. 17. It can
aluminum and precision machined. The top metal plate of be seen that although both antennas own the same cross
the antenna (etched with the slots) and the rest cavity struc- section dimension, the proposed antenna is shorter than the
ture (including the metallic sheets) are mechanically milled conventional antenna due to its smaller waveguide wavelength.
separately and then welded together to form the complete In the experiment, the reflection coefficients of both antennas
antenna. An additional flange connector is also soldered at are measured by an Agilent E8361C PNA, and the far-field
the antenna’s input port for the convenience of measurement. radiations are measured in a compact range chamber.
Moreover, for a better comparison, a K u-band eight-slot Fig. 18 shows the simulated and measured reflection coef-
conventional rectangular waveguide slot array antenna as the ficients of the proposed and conventional antennas. It is

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 YUAN et al.: RECTANGULAR GRATING WAVEGUIDE SLOT ARRAY ANTENNA FOR SATCOM APPLICATIONS 3877

well with the simulated ones. In the receiving frequencies,

the proposed and conventional antennas achieve flat measured
realized gains, whose peak values are 15.82 and 16.36 dBi,
respectively. In the transmitting frequencies, the measured
realized gains of the proposed and conventional antennas are
from −10.77 to −22.16 dBi and from 4.07 to −0.84 dBi,
respectively. The proposed antenna achieves an additional 14.8
to 21.3 dB realized gain suppression in 14.0–14.5 GHz relative
to the conventional antenna. An example of the radiation
patterns in H-plane at 14.25 GHz of both antennas is shown
in Fig. 19, where the peak values are −17.7 and 1.9 dBi,
respectively. It is inferred that the realized gain suppression
is approximately 19.6 dB. In most directions, the proposed
antenna shows the apparent radiation suppressions compared
with the conventional antenna, which confirms its extra filter-
Fig. 19. Simulated and measured realized gains of the proposed and
ing response. In addition, it is noted that the measured realized
conventional antennas. gains of the proposed antenna are ∼3.7 dB higher than the
simulated ones at around 14.0 GHz. This may be caused by
the slight shape distortions of some milled metallic sheets due
to the fabrication tolerance, which may result in relatively large
errors in some frequencies, like 14.0 GHz. Also, the antenna
beam steering error in radiation measurement may also be
a factor responsible for the antenna realized gain measuring
errors.
To discuss the efficiency of the proposed antenna, the
efficiencies of the proposed and conventional antennas are
compared, as shown in Fig. 20. Here, the antenna efficiency is
estimated by dividing the antenna measured realized gain G
by the aperture directivity D0 [32]
G Gλ20
Efficiency = × 100% = × 100% (3)
D0 4π Ae
Fig. 20. Measured antenna efficiencies of the proposed and conventional
antennas.
where λ0 is the wavelength in free space and Ae is the antenna
aperture calculated by
Ae = (4 × λg,12.5GHz ) × a = (8 × ps ) × a. (4)
observed that a good agreement between the simulated and
measured results is achieved. The measured −15 dB band- Considering that each of the eight slots occupies the length
width of the proposed antenna is 6.4% (12.03–12.83 GHz), of half a waveguide wavelength at 12.5 GHz, we use the
and the corresponding results of the conventional antenna are range of four waveguide wavelengths to represent the antenna
6.0% (12.05–12.80 GHz). Both antennas operate well in the aperture. As can be seen, in the receiving frequencies, the pro-
receiving frequencies of 12.25–12.75 GHz. On the other hand, posed antenna achieves the total efficiency of 68.3%–88.8%,
in the transmitting frequencies of 14.0–14.5 GHz, the mea- while the conventional antenna achieves the total efficiency
sured reflection coefficients of the proposed and conventional of 66.9%–84.6%. The proposed antenna performs the similar
antennas are larger than −0.80 and −1.93 dB, respectively. antenna efficiency as that of the conventional antenna. This
This implies that the proposed antenna has a better out-of- can be explained as follows. On the one hand, the metallic
band rejection performance. In addition, it can be seen that sheets introduce extra metal loss to the proposed antenna,
there exist two resonances of the proposed antenna at 13.34 which reduces the efficiency of the proposed antenna of about
and 13.64 GHz. They are mainly formed by the metallic sheets 2%. On the other hand, a shorter waveguide wavelength of the
and the shorted waveguide and can be tuned by adjusting the proposed antenna contributes to a more uniform current dis-
distance d1 between the innermost metallic sheet and the short tribution. Instead, this increases the efficiency of the antenna
wall. Nevertheless, their existences do not influence the out- aperture. It is inferred that the introduction of an extra filtering
of-band rejection of the proposed antenna. response almost not sacrifice the antenna efficiency. Moreover,
More specifically, Fig. 19 shows the simulated and measured the proposed antenna only has its weight increased by 3% by
realized gains of the proposed and conventional antennas. introducing the metallic sheets.
The realized gains are represented by the peak values of the Moreover, Fig. 21 shows the normalized radiation patterns
radiation patterns in H-plane of both antennas since they are of both antennas at 12.5 GHz. It can be seen that both anten-
both linear slot arrays and have wide E-plane beam widths. nas show good broadside radiation patterns in the H-plane.
As can be observed, the measured results generally agree The measured sidelobe levels of both antennas are lower

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 3878 IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. 67, NO. 6, JUNE 2019

Fig. 21. Simulated and measured normalized radiation patterns at 12.5 GHz in (a) H-plane of the proposed antenna, (b) E-plane of the proposed antenna,
(c) H-plane of the conventional antenna, and (d) E-plane of the conventional antenna.

than −12 dB. Compared with the conventional antenna, the TABLE IV
proposed antenna shows a wider main lobe, which is caused C OMPARISON W ITH O THER F ILTERING WAVEGUIDE
S LOT A RRAY A NTENNAS
by its smaller antenna aperture. It is noted that the proposed
antenna shows an asymmetric radiation pattern in H-plane.
This is mainly resulted by the asymmetric metallic sheets
inside the antenna, which cause different coupling effects
to the radiating slots. In the practical large-scale planar slot
array design, this asymmetry can be overcome by placing
two of the proposed linear arrays in a symmetric manner.
Besides, this asymmetry may also be resulted by the attached
flange connector, which is similar for the conventional antenna.
In addition, the cross-polarization levels of both antennas are
better than −29 and −45 dB for measurement and simulation,
respectively. The measured results are degraded compared with
the simulated ones, which is mainly caused by the measur-
ing errors in the measurements where there are difficulties
to set the linear-polarized antennas perfectly horizontally or
vertically. Nevertheless, the proposed antenna shows a good
radiation performance as the conventional antenna does.
Furthermore, a comparison of the proposed antenna with the
other three reported filtering waveguide slot array antennas is waveguide to achieve an extra filtering response. Therefore, the
conducted, and the results are listed in Table IV. Different proposed antenna is able to combine the filtering integration
from the antennas in [21], [22], and [24], which integrate methods in [21], [22], and [24] when constructing a large
the filtering structure into their feed waveguide, the proposed array, which can further improve the filtering performance.
antenna integrates the filtering structure into the radiation Moreover, although all the antennas show good measured

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 YUAN et al.: RECTANGULAR GRATING WAVEGUIDE SLOT ARRAY ANTENNA FOR SATCOM APPLICATIONS 3879

efficiencies, the proposed antenna achieves a slightly higher [12] H.-T. Hu, F.-C. Chen, J.-F. Qian, and Q.-X. Chu, “A differential
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 3880 IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. 67, NO. 6, JUNE 2019

Weile Yuan was born in Dongguan, Guangdong, Junping Geng (M’08–SM’17) received the B.S.
China, in 1993. He received the B.S. degree in degree in plastic working of metals, M.S. degree in
information engineering from Shanghai Jiao Tong corrosion and protection of equipment, and Ph.D.
University (SJTU), Shanghai, China, in 2016, where degree in circuit and system from Northwestern
he is currently pursuing the M.S. degree under the Polytechnic University, Xi’an, China, in 1996, 1999,
supervision of Prof. X. Liang. and 2003, respectively.
His current research interests include filtering From 2003 to 2005, he was a Post-Doctoral
waveguide slot array antennas. Researcher with Shanghai Jiao Tong University,
Shanghai, China. In 2005, he joined the Faculty of
Electronic Engineering Department, Shanghai Jiao
Tong University, where he is currently an Associate
Professor. From 2010 to 2011, he was a Visiting Scholar with the Insti-
tute Electrical and Computer Engineering, University of Arizona, Tucson,
AZ, USA. He has authored or co-authored more than 300 refereed jour-
nal and conference papers, three book chapters, and one book. He holds
over 60 patents with over 40 pending. He has been involved in multiantennas
for terminals, smart antennas, and nanoantennas. His current research interests
include antennas, electromagnetic theory, and computational techniques of
electromagnetic and nanoantennas.
Dr. Geng is a member of the Chinese Institute of Electronics. He was
a recipient of the Technology Innovation Award of the Chinese Ministry
of Education in 2007 and a Technology Innovation Award of the Chinese
Government in 2008.
Xianling Liang (M’11–SM’17) received the B.S.
degree in electronic engineering from Xidian Uni- Weiren Zhu (M’16–SM’18) received the B.S. and
versity, Xi’an, China, in 2002, and the Ph.D. degree Ph.D. degrees in physics from Northwestern Poly-
in electric engineering from Shanghai University, technical University, Xi’an, China, in 2006 and
Shanghai, China, in 2007. 2011, respectively.
From 2007 to 2008, he was a Post-Doctoral From 2011 to 2012, he was a Post-Doctoral Fel-
Research Fellow with the Institute National de la low with the Nonlinear Physics Centre, Australian
Recherche Scientifique, University of Quebec, Mon- National University, Canberra, ACT, Australia.
treal, QC, Canada. In 2008, he joined the Depart- From 2012 to 2016, he was a Research Fellow with
ment of Electronic Engineering, Shanghai Jiao Tong the Advanced Computing and Simulation Labora-
University (SJTU), Shanghai, as a Lecturer, where tory (Aχ L), Department of Electrical and Computer
he became an Associate Professor in 2012. He has authored or co-authored Systems Engineering, Monash University, Clayton,
more than 250 papers including 141 journal papers and 113 conference VIC, Australia. Since 2016, he has been with the Department of Electronic
papers and co-authored one book and three chapters, in microwave and Engineering, Shanghai Jiao Tong University, Shanghai, China, as an Associate
antenna fields. He holds 15 patents in antenna and wireless technologies. His Professor. He has authored and co-authored more than 100 refereed journal
current research interests include OAM-EM wave propagation and antenna papers and more than 40 conference proceedings. His current research interests
design, time-modulated/4-D array and applications, anti-interference antenna include electromagnetic metamaterials, antennas and RF devices, and surface
and array, integrated active antenna and array, and ultrawideband wide-angle plasmon polaritons.
scanning phased array. Dr. Zhu is a senior member of the Optical Society of America. He was a
Dr. Liang was a recipient of the Award of Shanghai Municipal Excellent recipient of the Shanghai Pujiang Talent Program by Shanghai Science and
Doctoral Dissertation in 2008, the Nomination of the National Excellent Doc- Technology Commission in 2017. He is currently serving as an Associate
toral Dissertation in 2009, the Best Paper Award presented at the International Editor for the IEEE P HOTONICS J OURNAL, an Associate Editor for IEEE
Workshop on Antenna Technology: Small Antennas, Innovative Structures, A CCESS , and a Guest Editor for Journal of Physics: Condensed Matter.
and Materials in 2010, the SMC Excellent Young Faculty and the Excellent
Teacher Award of SJTU in 2012, the Shanghai Natural Science Award in Ronghong Jin (M’09–SM’13–F’17) received the
2013, the Best Paper Award presented at the IEEE International Symposium B.S. degree in electronic engineering, M.S. degree
on Microwave, Antenna, Propagation, and EMC Technologies in 2015, and in electromagnetic and microwave technology, and
the 4th China Publishing Government Book Award and the Okawa Foundation Ph.D. degree in communication and electronic sys-
Research Grant recipient in 2017. tems from Shanghai Jiao Tong University (SJTU),
Shanghai, China, in 1983, 1986, and 1993, respec-
tively.
In 1986, he joined the Department of Electronic
Engineering, SJTU, where he was an Assistant,
a Lecturer, and an Associate Professor and is cur-
rently a Professor. From 1997 to 1999, he was a
Visiting Scholar with the Department of Electrical and Electronic Engineer-
ing, Tokyo Institute of Technology, Meguro, Japan. From 2001 to 2002,
he was a Special Invited Research Fellow with the Communication Research
Laboratory, Tokyo, Japan. From 2006 to 2009, he was a Guest Professor
with the University of Wollongong, Wollongong, NSW, Australia. He is
also a Distinguished Guest Scientist with the Commonwealth Scientific and
Industrial Research Organization, Sydney, NSW, Australia. He has authored
Lina Zhang received the B.S. degree from and co-authored more than 400 papers in refereed journals and conference
Northwestern Polytechnic University, Xi’an, China, proceedings and co-authored seven books. He holds more than 70 patents
in 2005, and the Ph.D. degree from Shanghai Uni- in antenna and wireless technologies. His current research interests include
versity, Shanghai, China, in 2011, both in electrical antennas, electromagnetic theory, numerical techniques of solving field prob-
engineering. lems, and wireless communications.
She is currently an Antenna Senior Engineer with Dr. Jin is a Committee Member of the Antenna Branch of the Chi-
the Research Institute of Shanghai Aerospace Elec- nese Institute of Electronics, Beijing, China. He was a recipient of the
tronic Communication Equipment, Shanghai. She National Technology Innovation Award, the National Nature Science Award,
has authored or co-authored more than 20 jour- the 2012 Nomination of National Excellent Doctoral Dissertation (Supervisor),
nal papers and 10 conference papers. Her current the 2017 Excellent Doctoral Dissertation (Supervisor) of China Institute of
research interests include waveguide slot antennas, Communications, the Shanghai Nature Science Award, and the Shanghai
microstrip antennas, and microwave passive devices and circuits. Science and Technology Progress Award.

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