LTC6101/LTC6101HV

High Voltage,
High-Side Current Sense
Amplifier in SOT-23
FEATURES DESCRIPTION
n Supply Range: The LTC®6101/LTC6101HV are versatile, high voltage, high
5V to 100V, 105V Absolute Maximum (LTC6101HV) side current sense amplifiers. Design flexibility is provided
4V to 60V, 70V Absolute Maximum (LTC6101) by the excellent device characteristics; 300μV Max offset
n Low Offset Voltage: 300μV Max and only 375μA (typical at 60V) of current consumption.
n Fast Response: 1μs Response Time (0V to 2.5V on The LTC6101 operates on supplies from 4V to 60V and
a 5V Output Step) LTC6101HV operates on supplies from 5V to 100V.
n Gain Configurable with 2 Resistors
n Low Input Bias Current: 170nA Max
The LTC6101 monitors current via the voltage across an
n PSRR: 118dB Min
external sense resistor (shunt resistor). Internal circuitry
converts input voltage to output current, allowing for a
n Output Current: 1mA Max
small sense signal on a high common mode voltage to
n Low Supply Current: 250μA, V­ = 12V
S be translated into a ground referenced signal. Low DC
n Specified Temperature Range: –40°C to 125°C
offset allows the use of a small shunt resistor and large
n Operating Temperature Range: –55°C to 125°C
gain-setting resistors. As a result, power loss in the shunt
n Package Option for High Voltage Spacing
is reduced.
n Low Profile (1mm) SOT-23 (ThinSOT™) Package
The wide operating supply range and high accuracy make
the LTC6101 ideal for a large array of applications from
APPLICATIONS automotive to industrial and power management. A maxi-
n Current Shunt Measurement mum input sense voltage of 500mV allows a wide range
n Battery Monitoring of currents to be monitored. The fast response makes the
n Remote Sensing LTC6101 the perfect choice for load current warnings and
n Power Management shutoff protection control. With very low supply current,
the LTC6101 is suitable for power sensitive applications.
All registered trademarks and trademarks are the property of their respective owners.
The LTC6101 is available in 5-lead SOT-23 and 8-lead
MSOP packages.

TYPICAL APPLICATION
16-Bit Resolution Unidirectional Output into LTC2433 ADC
Step Response
ILOAD VSENSE
– +
VSENSE–
RIN 5V TO 105V
100Ω ΔVSENSE– = 100mV
+IN
–IN
5.5V
L
V– + – V+ 5V
O
A 5V 1µF TA = 25°C
D V+ = 12V
RIN = 100
VOUT ROUT = 5k
OUT
VOUT VSENSE+ = V+
LTC6101HV
IOUT = 100µA
LTC2433-1 TO µP
ROUT 0.5V IOUT = 0
4.99k 0V
500ns/DIV
6101 TA01
6101 TA01b
ROUT
VOUT = • VSENSE = 49.9VSENSE
RIN
Rev I

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LTC6101/LTC6101HV
ABSOLUTE MAXIMUM RATINGS
(Note 1)
Total Supply Voltage (V+ to V–) LTC6101I/LTC6101HVI.......................... –40°C to 85°C
LTC6101................................................................ 70V LTC6101H/LTC6101HVH.................... –55°C to 125°C
LTC6101HV......................................................... 105V Specified Temperature Range (Note 2)
Minimum Input Voltage (–IN Pin)..................... (V+ – 4V) LTC6101C/LTC6101HVC............................ 0°C to 70°C
Maximum Output Voltage (Out Pin).............................9V LTC6101I/LTC6101HVI.......................... –40°C to 85°C
Input Current........................................................ ±10mA LTC6101H/LTC6101HVH.................... –40°C to 125°C
Output Short-Circuit Duration (to V–)............... Indefinite Storage Temperature Range................... –65°C to 150°C
Operating Temperature Range Lead Temperature (Soldering, 10 sec).................. 300°C
LTC6101C/LTC6101HVC........................– 40°C to 85°C

PIN CONFIGURATION
VHV PINOUT

TOP VIEW
TOP VIEW
TOP VIEW
+IN 1 5 OUT
–IN 1 8 +IN OUT 1 5 V+
NC 2 7 V+ –IN 2
V– 2
NC 3 6 NC
V+ 3 4 V–
OUT 4 5 V– –IN 3 4 +IN

MS8 PACKAGE S5 PACKAGE

S5 PACKAGE 5-LEAD PLASTIC TSOT-23
8-LEAD PLASTIC MSOP
TJMAX = 150°C, θJA = 300°C/ W 5-LEAD PLASTIC TSOT-23 TJMAX = 150°C, JA = 250°C/W
TJMAX = 150°C, θJA = 250°C/ W

ORDER INFORMATION http://www.linear.com/product/LTC6101#orderinfo

LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION SPECIFIED TEMPERATURE RANGE
LTC6101ACMS8#PBF LTC6101ACMS8#TRPBF LTBSB 8-Lead Plastic MSOP 0°C to 70°C
LTC6101AIMS8#PBF LTC6101AIMS8#TRPBF LTBSB 8-Lead Plastic MSOP –40°C to 85°C
LTC6101AHMS8#PBF LTC6101AHMS8#TRPBF LTBSB 8-Lead Plastic MSOP –40°C to 125°C
LTC6101HVACMS8#PBF LTC6101HVACMS8#TRPBF LTBSX 8-Lead Plastic MSOP 0°C to 70°C
LTC6101HVAIMS8#PBF LTC6101HVAIMS8#TRPBF LTBSX 8-Lead Plastic MSOP –40°C to 85°C
LTC6101HVAHMS8#PBF LTC6101HVAHMS8#TRPBF LTBSX 8-Lead Plastic MSOP –40°C to 125°C

Rev I

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 LTC6101/LTC6101HV
ORDER INFORMATION
Lead Free Finish
TAPE AND REEL (MINI) TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION SPECIFIED TEMPERATURE RANGE
LTC6101ACS5#TRMPBF LTC6101ACS5#TRPBF LTBND 5-Lead Plastic TSOT-23 0°C to 70°C
LTC6101AIS5#TRMPBF LTC6101AIS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 85°C
LTC6101AHS5#TRMPBF LTC6101AHS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 125°C
LTC6101BCS5#TRMPBF LTC6101BCS5#TRPBF LTBND 5-Lead Plastic TSOT-23 0°C to 70°C
LTC6101BIS5#TRMPBF LTC6101BIS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 85°C
LTC6101BHS5#TRMPBF LTC6101BHS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 125°C
LTC6101CCS5#TRMPBF LTC6101CCS5#TRPBF LTBND 5-Lead Plastic TSOT-23 0°C to 70°C
LTC6101CIS5#TRMPBF LTC6101CIS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 85°C
LTC6101CHS5#TRMPBF LTC6101CHS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 125°C
LTC6101HVACS5#TRMPBF LTC6101HVACS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 0°C to 70°C
LTC6101HVAIS5#TRMPBF LTC6101HVAIS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 85°C
LTC6101HVAHS5#TRMPBF LTC6101HVAHS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 125°C
LTC6101HVBCS5#TRMPBF LTC6101HVBCS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 0°C to 70°C
LTC6101HVBIS5#TRMPBF LTC6101HVBIS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 85°C
LTC6101HVBHS5#TRMPBF LTC6101HVBHS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 125°C
LTC6101HVCCS5#TRMPBF LTC6101HVCCS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 0°C to 70°C
LTC6101HVCIS5#TRMPBF LTC6101HVCIS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 85°C
LTC6101HVCHS5#TRMPBF LTC6101HVCHS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 125°C
LTC6101VHVACS5#TRMPBF LTC6101VHVACS5#TRPBF LTHHD 5-Lead Plastic TSOT-23 HV Pinout 0°C to 70°C
LTC6101VHVAIS5#TRMPBF LTC6101VHVAIS5#TRPBF LTHHD 5-Lead Plastic TSOT-23 HV Pinout –40°C to 85°C
LTC6101VHVAHS5#TRMPBF LTC6101VHVAHS5#TRPBF LTHHD 5-Lead Plastic TSOT-23 HV Pinout –40°C to 125°C
LTC6101VHVBCS5#TRMPBF LTC6101VHVBCS5#TRPBF LTHHD 5-Lead Plastic TSOT-23 HV Pinout 0°C to 70°C
LTC6101VHVBIS5#TRMPBF LTC6101VHVBIS5#TRPBF LTHHD 5-Lead Plastic TSOT-23 HV Pinout –40°C to 85°C
LTC6101VHVBHS5#TRMPBF LTC6101VHVBHS5#TRPBF LTHHD 5-Lead Plastic TSOT-23 HV Pinout –40°C to 125°C
LTC6101VHVCCS5#TRMPBF LTC6101VHVCCS5#TRPBF LTHHD 5-Lead Plastic TSOT-23 HV Pinout 0°C to 70°C
LTC6101VHVCIS5#TRMPBF LTC6101VHVCIS5#TRPBF LTHHD 5-Lead Plastic TSOT-23 HV Pinout –40°C to 85°C
LTC6101VHVCHS5#TRMPBF LTC6101VHVCHS5#TRPBF LTHHD 5-Lead Plastic TSOT-23 HV Pinout –40°C to 125°C
TRM = 500 pieces. *Temperature grades are identified by a label on the shipping container.
Consult ADI Marketing for parts specified with wider operating temperature ranges.
Consult ADI Marketing for information on lead based finish parts.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/

Rev I

For more information www.analog.com 3

LTC6101/LTC6101HV
ELECTRICAL CHARACTERISTICS
(LTC6101) The ● denotes the specifications which apply over the full
specified temperature range, otherwise specifications are at TA = 25°C, RIN = 100Ω, ROUT = 10k, VSENSE+ = V+ (see Figure 1 for
details), 4V ≤ VS ≤ 60V unless otherwise noted.
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
VS Supply Voltage Range ● 4 60 V
VOS Input Offset Voltage VSENSE = 5mV, Gain = 100, LTC6101A ±85 ±300 µV
VSENSE = 5mV, Gain = 100, LTC6101AC, LTC6101AI ● ±450 µV
VSENSE = 5mV, Gain = 100, LTC6101AH ● ±535 µV
VSENSE = 5mV, Gain = 100, LTC6101B ±150 ±450 µV
● ±810 µV
VSENSE = 5mV, Gain = 100, LTC6101C ±400 800 µV
● 1200 µV
∆VOS/∆T Input Offset Voltage Drift VSENSE = 5mV, LTC6101A ● ±1 µV/°C
VSENSE = 5mV, LTC6101B ● ±3 µV/°C
VSENSE = 5mV, LTC6101C ● ±5 µV/°C
IB Input Bias Current RIN = 1M 100 170 nA
● 245 nA
IOS Input Offset Current RIN = 1M ● ±2 ±15 nA
VSENSE(MAX) Input Sense Voltage Full Scale VOS within Specification, RIN = 1k (Note 3) ● 500 mV
PSRR Power Supply Rejection Ratio VS = 6V to 60V, VSENSE = 5mV, Gain = 100 118 140 dB
● 115 dB
VS = 4V to 60V, VSENSE = 5mV, Gain = 100 110 133 dB
● 105 dB
VOUT Maximum Output Voltage 12V ≤ VS ≤ 60V, VSENSE = 88mV ● 8 V
VS = 6V, VSENSE = 330mV, RIN = 1k, ROUT = 10k ● 3 V
VS = 4V, VSENSE = 550mV, RIN = 1k, ROUT = 2k ● 1 V
VOUT (0) Minimum Output Voltage VSENSE = 0V, Gain = 100, LTC6101A 0 30 mV
VSENSE = 0V, Gain = 100, LTC6101AC, LTC6101AI ● 45 mV
VSENSE = 0V, Gain = 100, LTC6101AH ● 53.5 mV
VSENSE = 0V, Gain = 100, LTC6101B 0 45 mV
● 81 mV
VSENSE = 0V, Gain = 100, LTC6101C 0 150 mV
● 250 mV
IOUT Maximum Output Current 6V ≤ VS ≤ 60V, ROUT = 2k, VSENSE = 110mV, Gain = 20 ● 1 mA
VS = 4V, VSENSE = 550mV, Gain = 2, ROUT = 2k ● 0.5 mA
tr Input Step Response ∆VSENSE = 100mV Transient, 6V ≤ VS ≤ 60V, Gain = 50 1 µs
(to 2.5V on a 5V Output Step) VS = 4V 1.5 µs
BW Signal Bandwidth IOUT = 200μA, RIN = 100, ROUT = 5k 140 kHz
IOUT = 1mA, RIN = 100, ROUT = 5k 200 kHz
IS Supply Current VS = 4V, IOUT = 0, RIN = 1M 220 450 µA
● 475 µA
VS = 6V, IOUT = 0, RIN = 1M 240 475 µA
● 525 µA
VS = 12V, IOUT = 0, RIN = 1M 250 500 µA
● 590 µA
VS = 60V, IOUT = 0, RIN = 1M 375 640 µA
LTC6101AI, LTC6101AC, LTC6101BI, LTC6101BC,
LTC6101CI, LTC6101CC ● 690 µA
LTC6101AH, LTC6101BH, LTC6101CH ● 720 µA

Rev I

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 LTC6101/LTC6101HV
ELECTRICAL CHARACTERISTICS
(LTC6101HV) The ● denotes the specifications which apply over the full
specified temperature range, otherwise specifications are at TA = 25°C, RIN = 100Ω, ROUT = 10k, VSENSE+ = V+ (see Figure 1 for
details), 5V ≤ VS ≤ 100V unless otherwise noted.
SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS
VS Supply Voltage Range ● 5 100 V
VOS Input Offset Voltage VSENSE = 5mV, Gain = 100, LTC6101HVA ±85 ±300 µV
VSENSE = 5mV, Gain = 100, LTC6101HVAC, LTC6101HVAI ● ±450 µV
VSENSE = 5mV, Gain = 100, LTC6101HVAH ● ±535 µV
VSENSE = 5mV, Gain = 100, LTC6101HVB ±150 ±450 µV
● ±810 µV
VSENSE = 5mV, Gain = 100, LTC6101HVC ±400 800 µV
● 1200 µV
∆VOS/∆T Input Offset Voltage Drift VSENSE = 5mV, LTC6101HVA ● ±1 µV/°C
VSENSE = 5mV, LTC6101HVB ● ±3 µV/°C
VSENSE = 5mV, LTC6101HVC ● ±5 µV/°C
IB Input Bias Current RIN = 1M 100 170 nA
● 245 nA
IOS Input Offset Current RIN = 1M ● ±2 ±15 nA
VSENSE(MAX) Input Sense Voltage Full Scale VOS within Specification, RIN = 1k (Note 3) ● 500 mV
PSRR Power Supply Rejection Ratio VS = 6V to 100V, VSENSE = 5mV, Gain = 100 118 140 dB
● 115 dB
VS = 5V to 100V, VSENSE = 5mV, Gain = 100 110 133 dB
● 105 dB
VOUT Maximum Output Voltage 12V ≤ VS ≤ 100V, VSENSE = 88mV ● 8 V
VS = 5V, VSENSE = 330mV, RIN = 1k, ROUT = 10k ● 3 V
VOUT (0) Minimum Output Voltage VSENSE = 0V, Gain = 100, LTC6101HVA 0 30 mV
VSENSE = 0V, Gain = 100, LTC6101HVAC, LTC6101HVAI ● 45 mV
VSENSE = 0V, Gain = 100, LTC6101HVAH ● 53.5 mV
VSENSE = 0V, Gain = 100, LTC6101HVB 0 45 mV
● 81 mV
VSENSE = 0V, Gain = 100, LTC6101HVC 0 150 mV
● 250 mV
IOUT Maximum Output Current 5V ≤ VS ≤ 100V, ROUT = 2k, VSENSE = 110mV, Gain = 20 ● 1 mA
tr Input Step Response ∆VSENSE = 100mV Transient, 6V ≤ VS ≤ 100V, Gain = 50 1 µs
(to 2.5V on a 5V Output Step) VS = 5V 1.5 µs
BW Signal Bandwidth IOUT = 200μA, RIN = 100, ROUT = 5k 140 kHz
IOUT = 1mA, RIN = 100, ROUT = 5k 200 kHz
IS Supply Current VS = 5V, IOUT = 0, RIN = 1M 200 450 µA
● 475 µA
VS = 6V, IOUT = 0, RIN = 1M 220 475 µA
● 525 µA
VS = 12V, IOUT = 0, RIN = 1M 230 500 µA
● 590 µA
VS = 60V, IOUT = 0, RIN = 1M 350 640 µA
LTC6101HVI, LTC6101HVC ● 690 µA
LTC6101HVH ● 720 µA
VS = 100V, IOUT = 0, RIN = 1M 350 640 µA
LTC6101HVAI, LTC6101HVAC, LTC6101HVBI,
LTC6101HVBC, LTC6101HVCI, LTC6101HVCC ● 690 µA
LTC6101HVAH, LTC6101HVBH, LTC6101HVCH ● 720 µA

Rev I

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 LTC6101/LTC6101HV
ELECTRICAL CHARACTERISTICS
Note 1: Stresses beyond those listed under Absolute Maximum Ratings characterized and expected to meet specified performance from –40°C to
may cause permanent damage to the device. Exposure to any Absolute 85°C but are not tested or QA sampled at these temperatures. LTC6101I/
Maximum Rating condition for extended periods may affect device LTC6101HVI are guaranteed to meet specified performance from –40°C
reliability and lifetime. to 85°C. The LTC6101H/LTC6101HVH are guaranteed to meet specified
Note 2: The LTC6101C/LTC6101HVC are guaranteed to meet specified performance from –40°C to 125°C.
performance from 0°C to 70°C. The LTC6101C/LTC6101HVC are designed, Note 3: ROUT = 10k for 6V ≤ VS ≤ 100V, ROUT = 2k for VS = 4V.

TYPICAL PERFORMANCE CHARACTERISTICS

Input VOS vs Temperature Input VOS vs Supply Voltage Input Sense Range
800 40 2.5
REPRESENTATIVE TA = 25°C TA = 0°C TA = –40°C
600 UNITS 20
TA = 0°C
400 0 2

MAXIMUM VSENSE (V)

TA = 70°C
INPUT OFFSET (µV)

–20 TA = –40°C
INPUT OFFSET (µV)

200
1.5
0 –40
TA = 25°C
–60 TA = 125°C
–200 TA = 85°C
1
–400 –80
TA = 85°C
–600 –100 RIN = 100
RIN = 100 0.5
A GRADE ROUT = 5k
–800 B GRADE ROUT = 5k –120 VIN = 5mV RIN = 3k
TA = 125°C LTC6101
C GRADE VIN = 5mV LTC6101HV ROUT = 3k
–1000 –140 0
–40 –20 0 20 40 60 80 100 120 4 11 18 25 32 39 46 53 60 4 10 20 30 40 50 60 70 80 90 100
TEMPERATURE (°C) VSUPPLY (V) VSUPPLY (V)
6101 G02 6101 G05
6101 G01

LTC6101: VOUT Maximum LTC6101HV: VOUT Maximum LTC6101: IOUT Maximum

vs Temperature vs Temperature vs Temperature
12 12 7
VS = 60V VS = 100V
VS = 12V
10 10 6
VS = 12V VS = 12V
MAXIMUM OUTPUT (V)

MAXIMUM OUTPUT (V)

5 VS = 60V
MAXIMUM IOUT (mA)

8 8
4
6 VS = 6V
6
VS = 6V VS = 5V 3 VS = 6V
4 4 VS = 4V
VS = 4V 2
VS = 4V
2 2 1

0 0 0
–40 –20 0 20 40 60 80 100 120 –40 –20 0 20 40 60 80 100 120 –40 –20 0 20 40 60 80 100 120
TEMPERATURE (°C) TEMPERATURE (°C) TEMPERATURE (°C)
6101 G06 6101 G20 6101 G07

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 LTC6101/LTC6101HV
TYPICAL PERFORMANCE CHARACTERISTICS
LTC6101HV: IOUT Maximum Output Error Due to Input Offset
vs Temperature vs Input Voltage Gain vs Frequency
7 100 40
TA = 25°C
GAIN =10 35
6 IOUT = 1mA
VS = 12V TA = 25°C
30
10 RIN = 100
5 25 ROUT = 4.99k
MAXIMUM IOUT (mA)

OUTPUT ERROR (%)

VS = 100V
20

GAIN (dB)
4
1 15
VS = 6V IOUT = 200µA
3
10
VS = 5V
2 C GRADE 5
0.1 B GRADE
VS = 4V 0
1
A GRADE –5
0 0.01 –10
–40 –20 0 20 40 60 80 100 120 0 0.05 0.1 0.15 0.2 0.25 0.3 0.35 0.4 0.45 0.5 1k 10k 100k 1M
TEMPERATURE (°C) INPUT VOLTAGE (V) FREQUENCY (Hz)
6101 G21 6101 G08 6101 G09

Input Bias Current LTC6101: Supply Current LTC6101HV: Supply Current

vs Temperature vs Supply Voltage vs Supply Voltage
160 450 600
70°C
140 400 85°C
125°C 500 70°C
350 85°C
120
SUPPLY CURRENT (µA)

SUPPLY CURRENT (µA)

VS = 6V TO 100V
300 400 125°C
100
VS = 4V 250
IB (nA)

80 25°C 300
200
60 0°C 25°C
150 200
–40°C 0°C
40 –40°C
100
VIN = 0 100 VIN = 0
20 50 RIN = 1M RIN = 1M
0 0 0
–40 –20 0 20 40 60 80 100 120 0 4 8 12 16 20 24 28 32 36 40 44 48 52 56 60 0 10 20 30 40 50 60 70 80 90 100
TEMPERATURE (°C) SUPPLY VOLTAGE (V) SUPPLY VOLTAGE (V)
6101 G10
6101 G11 6101 G22

Step Response 0mV to 10mV Step Response 10mV to 20mV

–
VSENSE V+-10mV VSENSE–
V+
+
+
V -10mV V -20mV

0.5V 1V TA = 25°C
TA = 25°C
V+ = 12V
V+ = 12V
RIN = 100
RIN = 100
ROUT = 5k
ROUT = 5k
VSENSE+ = V+
VSENSE+ = V+

0V VOUT 0.5V VOUT

TIME (10µs/DIV) TIME (10µs/DIV)

6101 G12 6101 G13

Rev I

For more information www.analog.com 7

LTC6101/LTC6101HV
TYPICAL PERFORMANCE CHARACTERISTICS
Step Response 100mV Step Response 100mV Step Response Rising Edge
VSENSE– VSENSE– VSENSE–
V+ V+
ΔVSENSE– =100mV
V+-100mV V+-100mV TA = 25°C
CLOAD = 10pF V+ = 12V
5V 5V CLOAD = 2200pF 5.5V
TA = 25°C RIN = 100
V+ = 12V 5V
ROUT = 5k
RIN = 100 VSENSE+ = V+ TA = 25°C
ROUT = 5k V+ = 12V
CLOAD = 1000pF VSENSE+ = V+ RIN = 100
VOUT ROUT = 5k
VSENSE+ = V+
IOUT = 100µA

0V 0V VOUT 0.5V IOUT = 0

VOUT
0V

TIME (10µs/DIV) TIME (100µs/DIV) TIME (500ns/DIV)

6101 G14 6101 G15 6101 G16

Step Response Falling Edge PSRR vs Frequency

160

140 LTC6101,
ΔVSENSE– =100mV V+ = 4V

VOUT 120
5.5V
5V TA = 25°C 100 LTC6101,
V+ = 12V
PSRR (dB)

LTC6101HV,
RIN = 100 80 V+ = 12V
ROUT = 5k
VSENSE+ = V+
60 R = 100
IN
ROUT = 10k
IOUT = 100µ 40 C
OUT = 5pF
GAIN = 100 LTC6101HV,
20 I V+ = 5V
0.5V OUTDC = 100µA
IOUT = 0 VINAC = 50mVp
0V 0
0.1 1 10 100 1k 10k 100k 1M
TIME (500ns/DIV) FREQUENCY (Hz)
6101 G17 6101 G19

Rev I

8 For more information www.analog.com

 LTC6101/LTC6101HV
PIN FUNCTIONS
OUT: Current Output. OUT will source a current that is V+: Positive Supply Pin. Supply current is drawn through
proportional to the sense voltage into an external resistor. this pin. The circuit may be configured so that the
LTC6101 supply current is or is not monitored along
V – : Negative Supply (or Ground for Single-Supply
Operation). with the system load current. To monitor only system
load current, connect V+ to the more positive side of the
–IN: The internal sense amplifier will drive IN– to the same sense resistor. To monitor the total current, including the
potential as IN+. A resistor (RIN) tied from V+ to IN– sets LTC6101 current, connect V+ to the more negative side
the output current IOUT = VSENSE/RIN. VSENSE is the voltage of the sense resistor.
developed across the external RSENSE (Figure 1).
+IN: Must be tied to the system load end of the sense
resistor, either directly or through a resistor.

BLOCK DIAGRAM
ILOAD VSENSE
– +
VBATTERY
RSENSE V+
RIN
10V
L
O
A
D
–IN 5k –

+IN 5k +
10V IOUT
OUT ROUT
VOUT = VSENSE x
RIN
LTC6101/LTC6101HV V–
ROUT
6101 BD

Figure 1. LTC6101/LTC6101HV Block Diagram and Typical Connection

APPLICATIONS INFORMATION
The LTC6101 high side current sense amplifier (Figure 1) tor, RIN, between IN– and V+ forces a potential across
provides accurate monitoring of current through a user- RIN that is the same as the sense voltage across
selected sense resistor. The sense voltage is amplified by RSENSE. A corresponding current, V SENSE/RIN, will
a user-selected gain and level shifted from the positive flow through RIN. The high impedance inputs of the
power supply to a ground-referred output. The output sense amplifier will not conduct this input current,
signal is analog and may be used as is or processed with so it will flow through an internal MOSFET to the output pin.
an output filter.
The output current can be transformed into a voltage by
Theory of Operation adding a resistor from OUT to V –. The output voltage is
then VO = V– + IOUT • ROUT.
An internal sense amplifier loop forces IN– to have the
same potential as IN+. Connecting an external resis-
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LTC6101/LTC6101HV
APPLICATIONS INFORMATION
Useful Gain Configurations Peak dissipation is 200mW. If a 5mΩ sense resistor is
employed, then the effective current error is 30mA, while
Gain RIN ROUT VSENSE at VOUT = 5V IOUT at VOUT = 5V the peak sense voltage is reduced to 10mV at 2A, dis-
20 499 10k 250mV 500µA sipating only 20mW.
50 200 10k 100mV 500µA
The low offset and corresponding large dynamic range of
100 100 10k 50mV 500µA
the LTC6101 make it more flexible than other solutions in
this respect. The 150µV typical offset gives 60dB of dy-
Selection of External Current Sense Resistor
namic range for a sense voltage that is limited to 150mV
The external sense resistor, RSENSE, has a significant effect max, and over 70dB of dynamic range if the rated input
on the function of a current sensing system and must be maximum of 500mV is allowed.
chosen with care.
Sense Resistor Connection
First, the power dissipation in the resistor should be
considered. The system load current will cause both heat Kelvin connection of the IN– and IN+ inputs to the sense
and voltage loss in RSENSE. As a result, the sense resis- resistor should be used in all but the lowest power ap-
tor should be as small as possible while still providing plications. Solder connections and PC board interconnec-
the input dynamic range required by the measurement. tions that carry high current can cause significant error
Note that input dynamic range is the difference between in measurement due to their relatively large resistances.
the maximum input signal and the minimum accurately One 10mm x 10mm square trace of one-ounce copper
reproduced signal, and is limited primarily by input DC is approximately 0.5mΩ. A 1mV error can be caused by
offset of the internal amplifier of the LTC6101. In addition, as little as 2A flowing through this small interconnect.
RSENSE must be small enough that VSENSE does not exceed This will cause a 1% error in a 100mV signal. A 10A load
the maximum input voltage specified by the LTC6101, even current in the same interconnect will cause a 5% error
under peak load conditions. As an example, an application for the same 100mV signal. By isolating the sense traces
may require that the maximum sense voltage be 100mV. from the high-current paths, this error can be reduced
If this application is expected to draw 2A at peak load, by orders of magnitude. A sense resistor with integrated
RSENSE should be no more than 50mΩ. Kelvin sense terminals will give the best results. Figure 2
illustrates the recommended method.
Once the maximum RSENSE value is determined, the mini-
mum sense resistor value will be set by the resolution or V+
dynamic range required. The minimum signal that can be
accurately represented by this sense amp is limited by the
RIN
input offset. As an example, the LTC6101B has a typical RSENSE
input offset of 150µV. If the minimum current is 20mA, a +IN –IN

sense resistor of 7.5mΩ will set VSENSE to 150µV. This is + –

LOAD
the same value as the input offset. A larger sense resistor V– V+
will reduce the error due to offset by increasing the sense
voltage for a given load current.
Choosing a 50mΩ RSENSE will maximize the dynamic range OUT
and provide a system that has 100mV across the sense LTC6101 VOUT
ROUT
resistor at peak load (2A), while input offset causes an
error equivalent to only 3mA of load current. 6101 F02

Figure 2. Kelvin Input Connection Preserves

Accuracy Despite Large Load Current

Rev I

10 For more information www.analog.com

 LTC6101/LTC6101HV
APPLICATIONS INFORMATION
Selection of External Input Resistor, RIN V+

The external input resistor, RIN, controls the transconduc-

tance of the current sense circuit. Since IOUT = VSENSE/RIN, RSENSE DSENSE
transconductance gm = 1/RIN. For example, if RIN = 100, 6101 F03a

then IOUT = VSENSE /100 or IOUT = 1mA for VSENSE = 100mV. LOAD

RIN should be chosen to allow the required resolution

Figure 3a. Shunt Diode Limits Maximum Input Voltage to Allow
while limiting the output current. At low supply voltage, Better Low Input Resolution Without Overranging
IOUT may be as much as 1mA. By setting RIN such that
the largest expected sense voltage gives IOUT = 1mA, then This approach can be helpful in cases where occasional
the maximum output dynamic range is available. Output large burst currents may be ignored. It can also be used
dynamic range is limited by both the maximum allowed in a multirange configuration where a low current circuit
output current and the maximum allowed output voltage, as is added to a high current circuit (Figure 3b). Note that
well as the minimum practical output signal. If less dynamic a comparator (LTC1540) is used to select the range, and
range is required, then RIN can be increased accordingly, transistor M1 limits the voltage across RSENSE LO.
reducing the max output current and power dissipation.
Care should be taken when designing the board layout
If low sense currents must be resolved accurately in a
for RIN, especially for small RIN values. All trace and inter-
system that has very wide dynamic range, a smaller RIN
connect impedances will increase the effective RIN value,
than the max current spec allows may be used if the max
causing a gain error. In addition, internal device resistance
current is limited in another way, such as with a Schottky
will add approximately 0.2Ω to RIN.
diode across RSENSE (Figure 3a). This will reduce the high
current measurement accuracy by limiting the result, while
increasing the low current measurement resolution.

CMPZ4697 VLOGIC
(3.3V TO 5V)
10k 7
M1 3
Si4465 +
VIN
4
ILOAD
RSENSE HI –
10m 8 Q1
5 CMPT5551
VOUT
RSENSE LO 40.2k 6
301 100m 301 301 301
4.7k
+IN –IN +IN –IN 1.74M
LTC1540
2 1 HIGH
V– + – V+ V– + – V+ RANGE
VIN
619k INDICATOR
(ILOAD > 1.2A)

OUT OUT HIGH CURRENT RANGE OUT

LTC6101 LTC6101
250mV/A

7.5k
VLOGIC

BAT54C
LOW CURRENT RANGE OUT
2.5V/A
R5
7.5k
(VLOGIC +5V) ≤ VIN ≤ 60V
0 ≤ ILOAD ≤ 10A 6101 F03b

Figure 3b. Dual LTC6101s Allow High-Low Current Ranging

Rev I

For more information www.analog.com 11

LTC6101/LTC6101HV
APPLICATIONS INFORMATION
Selection of External Output Resistor, ROUT Output Error, EOUT, Due to the Amplifier DC Offset
Voltage, VOS
The output resistor, ROUT, determines how the output cur-
rent is converted to voltage. VOUT is simply IOUT • ROUT. EOUT(VOS) = VOS • (ROUT/RIN)
In choosing an output resistor, the max output voltage The DC offset voltage of the amplifier adds directly to the
must first be considered. If the circuit that is driven by value of the sense voltage, VSENSE. This is the dominant
the output does not limit the output voltage, then ROUT error of the system and it limits the available dynamic
must be chosen such that the max output voltage does range. The paragraph “Selection of External Current Sense
not exceed the LTC6101 max output voltage rating. If the Resistor” provides details.
following circuit is a buffer or ADC with limited input range,
then ROUT must be chosen so that IOUT(MAX) • ROUT is less Output Error, EOUT, Due to the Bias Currents,
than the allowed maximum input range of this circuit. IB(+) and IB(–)

In addition, the output impedance is determined by ROUT. If The bias current IB(+) flows into the positive input of the
the circuit to be driven has high enough input impedance, internal op amp. IB(–) flows into the negative input.
then almost any useful output impedance will be accept- EOUT(IBIAS) = ROUT((IB(+) • (RSENSE/RIN) – IB(–))
able. However, if the driven circuit has relatively low input
Since IB(+) ≈ IB(–) = IBIAS, if RSENSE << RIN then,
impedance, or draws spikes of current, such as an ADC
might do, then a lower ROUT value may be required in order EOUT(IBIAS) ≈ –ROUT • IBIAS
to preserve the accuracy of the output. As an example, if For instance if IBIAS is 100nA and ROUT is 1kΩ, the output
the input impedance of the driven circuit is 100 times ROUT, error is 0.1mV.
then the accuracy of VOUT will be reduced by 1% since:
Note that in applications where RSENSE ≈ RIN, IB(+) causes
R OUT • RIN(DRIVEN) a voltage offset in RSENSE that cancels the error due to
VOUT = IOUT • IB(–) and EOUT(IBIAS) ≈ 0. In applications where RSENSE <
R OUT +RIN(DRIVEN)
RIN, the bias current error can be similarly reduced if an
100 external resistor RIN(+) = (RIN – RSENSE) is connected as
= IOUT • R OUT • = 0.99 •IOUT • R OUT
101 shown in Figure 4 below. Under both conditions:

Error Sources EOUT(IBIAS) = ± ROUT • IOS; IOS = IB(+) – IB(–)

V+
The current sense system uses an amplifier and resistors
to apply gain and level shift the result. The output is then RIN–
dependent on the characteristics of the amplifier, such as
gain and input offset, as well as resistor matching. RSENSE
RIN+
+IN –IN
Ideally, the circuit output is: + –
LOAD
R
VOUT = VSENSE • OUT ; VSENSE = R SENSE •ISENSE V– V+
RIN

In this case, the only error is due to resistor mismatch,
which provides an error in gain only. However, offset LTC6101
OUT
VOUT
voltage, bias current and finite gain in the amplifier cause ROUT

additional errors: RIN+ = RIN– – RSENSE

6101 F04

Figure 4. Second Input R Minimizes

Error Due to Input Bias Current
Rev I

12 For more information www.analog.com

 LTC6101/LTC6101HV
APPLICATIONS INFORMATION
If the offset current, IOS, of the LTC6101 amplifier is 2nA, The total power dissipated is the output dissipation plus
the 100 microvolt error above is reduced to 2 microvolts. the quiescent dissipation:
Adding RIN+ as described will maximize the dynamic PTOTAL = POUT + PQ
range of the circuit. For less sensitive designs, RIN+ is
not necessary. At maximum supply and maximum output current, the
total power dissipation can exceed 100mW. This will
Example: cause significant heating of the LTC6101 die. In order to
If an ISENSE range = (1A to 1mA) and (VOUT/ISENSE) = prevent damage to the LTC6101, the maximum expected
3V/1A dissipation in each application should be calculated. This
number can be multiplied by the θJA value listed in the
Then, from the Electrical Characteristics of the LTC6101,
package section on page 2 to find the maximum expected
RSENSE ≈ VSENSE (max) / ISENSE (max) = 500mV/1A =
500mΩ die temperature. This must not be allowed to exceed 150°C,
or performance may be degraded.
Gain = ROUT/RIN = VOUT (max) / VSENSE (max) =
As an example, if an LTC6101 in the S5 package is to be
3V/500mV = 6
run at 55V ±5V supply with 1mA output current at 80°C:
If the maximum output current, IOUT, is limited to 1mA,
PQ(MAX) = IDD(MAX) • V+(MAX) = 41.4mW
ROUT equals 3V/1mA ≈ 3.01 kΩ (1% value) and RIN =
3kΩ/6 ≈ 499Ω (1% value). POUT(MAX) = IOUT • V+(MAX) = 60mW
The output error due to DC offset is ±900µVolts (typ) and TRISE = θJA • PTOTAL(MAX)
the error due to offset current, IOS is 3k x 2nA = ±6µVolts TMAX = TAMBIENT + TRISE
(typical), provided RIN+ = RIN–.
TMAX must be < 150°C
The maximum output error can therefore reach ±906µVolts
or 0.03% (–70dB) of the output full scale. Considering PTOTAL(MAX) ≈ 96mW and the max die temp
the system input 60dB dynamic range (ISENSE = 1mA to will be 104°C
1A), the 70dB performance of the LTC6101 makes this If this same circuit must run at 125°C, the max die
application feasible. temp will increase to 150°C. (Note that supply current,
and therefore PQ, is proportional to temperature. Refer
Output Error, EOUT, Due to the Finite DC Open Loop
to Typical Performance Characteristics section.) In this
Gain, AOL, of the LTC6101 Amplifier
condition, the maximum output current should be reduced
This error is inconsequential as the AOL of the LTC6101 to avoid device damage. Note that the MSOP package
is very large. has a larger θJA than the S5, so additional care must be
taken when operating the LTC6101A/LTC6101HVA at high
Output Current Limitations Due to Power Dissipation temperatures and high output currents.
The LTC6101 can deliver up to 1mA continuous current to The LTC6101HV can be used at voltages up to 105V. This
the output pin. This current flows through RIN and enters the additional voltage requires that more power be dissipated
current sense amp via the IN(–) pin. The power dissipated for a given level of current. This will further limit the allowed
in the LTC6101 due to the output signal is: output current at high ambient temperatures.
POUT = (V–IN – VOUT) • IOUT It is important to note that the LTC6101 has been designed
Since V–IN ≈ V+, POUT ≈ (V+ – V OUT) • IOUT to provide at least 1mA to the output when required, and
can deliver more depending on the conditions. Care must
There is also power dissipated due to the quiescent sup- be taken to limit the maximum output current by proper
ply current: choice of sense resistor and, if input fault conditions exist,
PQ = IDD • V+ external clamps.
Rev I

For more information www.analog.com 13

LTC6101/LTC6101HV
APPLICATIONS INFORMATION
Output Filtering Input Common Mode Range
The output voltage, VOUT, is simply IOUT • ZOUT. This The inputs of the LTC6101 can function from 1.5V below
makes filtering straightforward. Any circuit may be used the positive supply to 0.5V above it. Not only does this
which generates the required ZOUT to get the desired filter allow a wide VSENSE range, it also allows the input refer-
response. For example, a capacitor in parallel with ROUT ence to be separate from the positive supply (Figure 5).
will give a low pass response. This will reduce unwanted Note that the difference between VBATT and V+ must be no
noise from the output, and may also be useful as a charge more than the common mode range listed in the Electrical
reservoir to keep the output steady while driving a switch- Characteristics table. If the maximum VSENSE is less than
ing circuit such as a mux or ADC. This output capacitor 500mV, the LTC6101 may monitor its own supply current,
in parallel with an output resistor will create a pole in the as well as that of the load (Figure 6).
output response at: VBATTERY

1
f –3dB =
2 • π • R OUT • C OUT RIN
RSENSE
+IN –IN

Useful Equations + –
V+
LOAD
V– V+
Input Voltage : VSENSE = ISENSE • R SENSE
VOUT
R
Voltage Gain : = OUT
VSENSE RIN OUT
LTC6101 VOUT
I R
Current Gain : OUT = SENSE
ROUT

ISENSE RIN 6101 F05

IOUT 1
Transconductance : = Figure 5. V+ Powered Separately from
VSENSE RIN Load Supply (VBATT)
VOUT R
Transimpedance : = R SENSE • OUT
ISENSE RIN
V+

RIN
RSENSE
+IN –IN

+ –
LOAD V– V+

OUT
LTC6101 VOUT
ROUT

6101 F06

Figure 6. LTC6101 Supply Current

Monitored with Load
Rev I

14 For more information www.analog.com

 LTC6101/LTC6101HV
APPLICATIONS INFORMATION
Reverse Supply Protection sheet. Note that the curves are labeled with respect to the
initial output currents.
Some applications may be tested with reverse-polarity
supplies due to an expectation of this type of fault during The speed is also affected by the external circuit. In this
operation. The LTC6101 is not protected internally from case, if the input changes very quickly, the internal ampli-
external reversal of supply polarity. To prevent damage that fier will slew the gate of the internal output FET (Figure 1)
may occur during this condition, a Schottky diode should in order to maintain the internal loop. This results in cur-
be added in series with V– (Figure 7). This will limit the rent flowing through RIN and the internal FET. This current
reverse current through the LTC6101. Note that this diode slew rate will be determined by the amplifier and FET
will limit the low voltage performance of the LTC6101 by characteristics as well as the input resistor, RIN. Using a
effectively reducing the supply voltage to the part by VD. smaller RIN will allow the output current to increase more
quickly, decreasing the response time at the output. This
In addition, if the output of the LTC6101 is wired to a device
will also have the effect of increasing the maximum output
that will effectively short it to high voltage (such as through current. Using a larger ROUT will decrease the response
an ESD protection clamp) during a reverse supply condi- time, since VOUT = IOUT • ROUT. Reducing RIN and increas-
tion, the LTC6101’s output should be connected through ing ROUT will both have the effect of increasing the voltage
a resistor or Schottky diode (Figure 8). gain of the circuit.
Response Time High Voltage Spacing
The LTC6101 is designed to exhibit fast response to inputs For applications with higher voltage, the TSOT-23 HV
for the purpose of circuit protection or signal transmission. pinout of the LTC6101HV eases the printed circuit board
This response time will be affected by the external circuit (PCB) layout burden. In the typical high side current
in two ways, delay and speed. sense configuration, the sense voltages will be at or very
If the output current is very low and an input transient near the supply; normally the sense difference voltage is
occurs, there may be an increased delay before the output small. Therefore V+, +IN and –IN will be roughly the same
voltage begins changing. This can be improved by increas- voltage. The TSOT-23 HV pinout provides connection for
ing the minimum output current, either by increasing these three pins on the left side (Top View). Because volt-
RSENSE or decreasing RIN. The effect of increased output age differences between these high side pins and the OUT
current is illustrated in the step response curves in the and V– pin may be high, the OUT and V– pin lie separately,
Typical Performance Characteristics section of this data on the right side of the package.

RSENSE RSENSE

R1 R1
100 100 VBATT
+IN –IN +IN –IN

L V– + – V+ L V– + – V+
O O
A A
D VBATT
D R3
1k
OUT OUT
LTC6101 LTC6101 ADC

D1 R2 D1 R2
4.99k 4.99k
6101 F08

6101 F07

Figure 7. Schottky Prevents Damage During Supply Reversal Figure 8. Additional Resistor R3 Protects Output During
Supply Reversal
Rev I

For more information www.analog.com 15

LTC6101/LTC6101HV
TYPICAL APPLICATIONS
Bidirectional Current Sense Circuit with Separate Charge/Discharge Output

IDISCHARGE RSENSE ICHARGE

CHARGER

RIN D RIN C
100 100
RIN D RIN C
+IN –IN 100 100 –IN +IN

VBATT
L V– + – V+ V+ – + V–
O
A
D
OUT OUT
LTC6101 LTC6101
+ +
ROUT D VOUT D VOUT C ROUT C
4.99k 4.99k
– –
6101 TA02

DISCHARGING: VOUT D = IDISCHARGE • RSENSE ( ROUT D

RIN D )
WHEN IDISCHARGE ≥ 0

CHARGING: VOUT C = ICHARGE • RSENSE ( ROUT C

RIN C )
WHEN ICHARGE ≥ 0

LTC6101 Monitors Its Own Supply Current High-Side-Input Transimpedance Amplifier

VS
ILOAD RSENSE

CMPZ4697* LASER MONITOR iPD

(10V) PHOTODIODE
R1 ISUPPLY
100
+IN –IN 4.75k 4.75k 10k

L +IN –IN
O
A V– + – V+
D
VBATT V– + – V+

OUT
LTC6101
+
R2 VOUT OUT
LTC6101 VO
4.99k
–
6101 TA03 RL

VO = IPD • RL
( )
6101 TA04
VOUT = 49.9 • RSENSE ILOAD + ISUPPLY *VZ SETS PHOTODIODE BIAS
VZ + 4 ≤ VS ≤ VZ + 60

Rev I

16 For more information www.analog.com

 LTC6101/LTC6101HV
TYPICAL APPLICATIONS
16-Bit Resolution Unidirectional Output into LTC2433 ADC

ILOAD VSENSE
– +
RIN 4V TO 60V
+IN –IN 100Ω

L
V– + – V+
O
A 5V 1µF
D
2 1
OUT VOUT 4 REF+ VCC
LTC6101 IN+ 9
SCK
8
LTC2433-1 SDD TO µP
ROUT – 7
4.99k IN CC
5
REF– GND FO
3 6 10
ROUT
VOUT = • VSENSE = 49.9VSENSE ADC FULL-SCALE = 2.5V 6101 TA06
RIN

Intelligent High-Side Switch with Current Monitor

10µF
VLOGIC 63V 14V

47k
100Ω V+
3 1%
FAULT 8 –IN

4 RS OUT
OFF ON LT1910 LTC6101 VO
6 +IN
2
100Ω 4.99k
1µF 1 5 V–
SUB85N06-5

L VO = 49.9 • RS • IL
O IL
A FOR RS = 5mΩ,
D VO = 2.5V AT IL = 10A (FULL SCALE)

6101 TA07

Rev I

For more information www.analog.com 17

LTC6101/LTC6101HV
TYPICAL APPLICATIONS
48V Supply Current Monitor with Isolated Output with 105V Survivability

VSENSE ISENSE
VS
+ –
LOAD
RSENSE
RIN
–IN +IN

V+ – + V–
V–

LTC6101HV
OUT VLOGIC

ROUT

VOUT

ANY OPTOISOLATOR

V–

N = OPTOISOLATOR CURRENT GAIN

R
VOUT = VLOGIC – ISENSE • SENSE • N • ROUT
RIN 6101 TA08

Simple 500V Current Monitor

DANGER! Lethal Potentials Present — Use Caution

ISENSE VSENSE 500V

– +
RSENSE RIN
+IN –IN 100Ω

L
V– + – V+ DANGER!!
O
A
HIGH VOLTAGE!!
D

OUT 62V
LTC6101
CMZ5944B

M1

VOUT M2

M1 AND M2 ARE FQD3P50 TM ROUT

2M
4.99k
ROUT
VOUT = • VSENSE = 49.9 VSENSE
RIN
6101 TA09

Rev I

18 For more information www.analog.com

 LTC6101/LTC6101HV
PACKAGE DESCRIPTION
Please refer to http://www.linear.com/product/LTC6101#packaging for the most recent package drawings.

MS8 Package
8-Lead Plastic MSOP
(Reference LTC DWG # 05-08-1660 Rev G)

0.889 ±0.127
(.035 ±.005)

5.10
(.201) 3.20 – 3.45
MIN (.126 – .136)

3.00 ±0.102
0.42 ± 0.038 0.65 (.118 ±.004) 0.52
(.0165 ±.0015) (.0256) (NOTE 3) 8 7 6 5 (.0205)
TYP BSC REF
RECOMMENDED SOLDER PAD LAYOUT

3.00 ±0.102
4.90 ±0.152
DETAIL “A” (.118 ±.004)
0.254 (.193 ±.006)
(NOTE 4)
(.010)
0° – 6° TYP
GAUGE PLANE
1 2 3 4
0.53 ±0.152
(.021 ±.006) 1.10 0.86
(.043) (.034)
DETAIL “A” MAX REF
0.18
(.007)
SEATING
PLANE 0.22 – 0.38 0.1016 ±0.0508
(.009 – .015) (.004 ±.002)
TYP 0.65 MSOP (MS8) 0213 REV G
(.0256)
NOTE:
BSC
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX

Rev I

For more information www.analog.com 19

LTC6101/LTC6101HV
PACKAGE DESCRIPTION
Please refer to http://www.linear.com/product/LTC6101#packaging for the most recent package drawings.

S5 Package
5-Lead Plastic TSOT-23
(Reference LTC DWG # 05-08-1635 Rev B)

0.62 0.95
2.90 BSC
MAX REF
(NOTE 4)

1.22 REF

1.50 – 1.75
3.85 MAX 2.62 REF 1.4 MIN 2.80 BSC
(NOTE 4)

PIN ONE

RECOMMENDED SOLDER PAD LAYOUT 0.30 – 0.45 TYP

0.95 BSC
PER IPC CALCULATOR 5 PLCS (NOTE 3)

0.80 – 0.90

0.20 BSC 0.01 – 0.10

1.00 MAX
DATUM ‘A’

0.30 – 0.50 REF

0.09 – 0.20 1.90 BSC
NOTE: (NOTE 3) S5 TSOT-23 0302 REV B
1. DIMENSIONS ARE IN MILLIMETERS
2. DRAWING NOT TO SCALE
3. DIMENSIONS ARE INCLUSIVE OF PLATING
4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR
5. MOLD FLASH SHALL NOT EXCEED 0.254mm
6. JEDEC PACKAGE REFERENCE IS MO-193

Rev I

20 For more information www.analog.com

 LTC6101/LTC6101HV
REVISION HISTORY (Revision history begins at Rev H)

REV DATE DESCRIPTION PAGE NUMBER

H 03/12 Updated Features 1
Updated Absolute Maximum Ratings and changed Order Information 2
Changed operating temperature range to specified temperature range in Electrical Characteristics header 4, 5
Changed TA value in curve G02 from 45°C to 25°C 6
I 05/18 Adding new TSOT package option 1 to 3, 5 to 9,
13, 15, 18, 21

Rev I

Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog
Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications
For
subject to change without notice. No license is morebyinformation
granted implication orwww.analog.com
otherwise under any patent or patent rights of Analog Devices. 21
LTC6101/LTC6101HV
TYPICAL APPLICATION
Bidirectional Current Sense Circuit with Combined Charge/Discharge Output

IDISCHARGE RSENSE ICHARGE

CHARGER

RIN C
RIN D
RIN D RIN C
+IN –IN –IN +IN

VBATT
L V– + – V+ V+ – + V–
O
A
D
OUT OUT
LTC6101 LTC6101
+
VOUT ROUT
–
6101 TA05

DISCHARGING: VOUT = IDISCHARGE • RSENSE ( ROUT

RIN D )
WHEN IDISCHARGE ≥ 0

CHARGING: VOUT = ICHARGE • RSENSE ( ROUT

RIN C )
WHEN ICHARGE ≥ 0

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LTC2052
LTC4150 Coulomb Counter/Battery Gas Gauge Indicates Charge Quantity and Polarity
LT6100 Gain-Selectable High-Side Current Sense Amplifier 4.1V to 48V Operation, Pin-Selectable Gain: 10, 12.5, 20, 25, 40, 50V/V

Rev I

22
D16879-0-5/18(I)
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