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TPA3110D2
SLOS528E – JULY 2009 – REVISED NOVEMBER 2015

TPA3110D2 15-W Filter-Free Stereo Class-D Audio Power Amplifier With Speakerguard™
1 Features 3 Description
1• 15-W/ch into an 8-Ω Loads at 10% THD+N From The TPA3110D2 is a 15-W (per channel) efficient,
a 16-V Supply Class-D audio power amplifier for driving bridged-tied
stereo speakers. Advanced EMI Suppression
• 10-W/ch into 8-Ω Loads at 10% THD+N From a Technology enables the use of inexpensive ferrite
13-V Supply bead filters at the outputs while meeting EMC
• 30-W into a 4-Ω Mono Load at 10% THD+N From requirements. SpeakerGuard™ speaker protection
a 16-V Supply circuitry includes an adjustable power limiter and a
• 90% Efficient Class-D Operation Eliminates Need DC detection circuit. The adjustable power limiter
allows the user to set a "virtual" voltage rail lower
for Heat Sinks
than the chip supply to limit the amount of current
• Wide Supply Voltage Range Allows Operation through the speaker. The DC detect circuit measures
From 8 V to 26 V the frequency and amplitude of the PWM signal and
• Filter-Free Operation shuts off the output stage if the input capacitors are
damaged or shorts exist on the inputs.
• SpeakerGuard™ Speaker Protection Includes
Adjustable Power Limiter Plus DC Protection The TPA3110D2 can drive stereo speakers as low as
• Flow Through Pin Out Facilitates Easy Board 4 Ω. The high efficiency of the TPA3110D2, 90%,
Layout eliminates the need for an external heat sink when
playing music.
• Robust Pin-to-Pin Short Circuit Protection and
Thermal Protection With Auto Recovery Option The outputs are also fully protected against shorts to
GND, VCC, and output-to-output. The short-circuit
• Excellent THD+N / Pop-Free Performance protection and thermal protection includes an auto-
• Four Selectable, Fixed Gain Settings recovery feature.
• Differential Inputs
Device Information(1)
2 Applications PART NUMBER PACKAGE BODY SIZE (NOM)
TPA3110D2 HTSSOP (28) 9.70 mm × 4.40 mm
• Televisions
• Consumer Audio Equipment (1) For all available packages, see the orderable addendum at
the end of the data sheet.

TPA3110D2 Simplified Application Schematic

1mF

OUTL+ LINP TPA3110D2

Audio OUTL- LINN
Source
OUTR+ RINP OUTPL FERRITE
15W
BEAD
OUTNL FILTER 8W
OUTR- RINN

GAIN0
GAIN1
OUTPR FERRITE
15W
BEAD
OUTNR FILTER 8W
PLIMIT
PBTL

Fault
SD PVCC 8 to 26V

An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
TPA3110D2
SLOS528E – JULY 2009 – REVISED NOVEMBER 2015 www.ti.com

Table of Contents
1 Features .................................................................. 1 9.2 Functional Block Diagram ....................................... 13
2 Applications ........................................................... 1 9.3 Feature Description................................................. 14
3 Description ............................................................. 1 9.4 Device Functional Modes........................................ 19
4 Revision History..................................................... 2 10 Application and Implementation........................ 20
10.1 Application Information.......................................... 20
5 Device Comparison Table..................................... 3
10.2 Typical Applications ............................................. 20
6 Pin Configuration and Functions ......................... 3
11 Power Supply Recommendations ..................... 24
7 Specifications......................................................... 4
11.1 Power Supply Decoupling, CS ............................. 24
7.1 Absolute Maximum Ratings ...................................... 4
7.2 ESD Ratings.............................................................. 5 12 Layout................................................................... 24
12.1 Layout Guidelines ................................................. 24
7.3 Recommended Operating Conditions...................... 5
12.2 Layout Example .................................................... 25
7.4 Thermal Information .................................................. 5
7.5 DC Characteristics: 24 V.......................................... 5 13 Device and Documentation Support ................. 26
7.6 DC Characteristics: 12 V.......................................... 6 13.1 Device Support .................................................... 26
7.7 AC Characteristics: 24 V.......................................... 6 13.2 Documentation Support ........................................ 26
7.8 AC Characteristics: 12 V.......................................... 6 13.3 Community Resources.......................................... 26
7.9 Typical Characteristics ............................................. 7 13.4 Trademarks ........................................................... 26
13.5 Electrostatic Discharge Caution ............................ 26
8 Parameter Measurement Information ................ 12
13.6 Glossary ................................................................ 26
9 Detailed Description ............................................ 13
9.1 Overview ................................................................. 13 14 Mechanical, Packaging, and Orderable
Information ........................................................... 26

4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.

Changes from Revision D (July 2012) to Revision E Page

• Added Pin Configuration and Functions section, ESD Ratings table, Feature Description section, Device Functional
Modes, Application and Implementation section, Power Supply Recommendations section, Layout section, Device
and Documentation Support section, and Mechanical, Packaging, and Orderable Information section .............................. 1

Changes from Revision C (August 2010) to Revision D Page

• Added < 10 V/ms to VI in the Absolute Maximum Ratings table, added Note 2 .................................................................... 4
• Changed the PBTL Select section. Added text - "The voltage slew.......series with the terminals." .................................... 18
• Added a 100kΩ resistor to AVCC Pin 14 and Note 1 to Figure 45 ...................................................................................... 23

Changes from Revision B (July 2010) to Revision C Page

• Replaced the Dissipations Ratings table with the Thermal Information table ........................................................................ 5

Changes from Revision A (July 2009) to Revision B Page

• Added slew rate adjustment information .............................................................................................................................. 16

• Added AVCC to Pin 7 of Figure 45 ...................................................................................................................................... 23

Changes from Original (July 2009) to Revision A Page

• Changed Changed the Stereo Class-D Amplifier with BTL Output and Single-Ended Input illustration Figure 41 -
Corrected the pin names. ..................................................................................................................................................... 20
• Changed Changed the Stereo Class-D Amplifier with PBTL Output and Single-Ended Input illustration Figure 45 -
Corrected the pin names. ..................................................................................................................................................... 23

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5 Device Comparison Table

DEVICE SPEAKER AMP

SPEAKER CHANNELS OUTPUT POWER (W) ADDITIONAL FEATURES
NUMBER TYPE
TPA3110D2 Stereo Class D 15 Power limiter
TPA3130D1 Stereo Class D 15
TPA3118D2 Stereo Class D 30 Power limiter
TPA3116D1 Stereo Class D 50 Power limiter

6 Pin Configuration and Functions

PWP Package
28-Pin HTSSOP With PowerPAD™
Top View

SD 1 28 PVCCL
FAULT 2 27 PVCCL
LINP 3 26 BSPL
LINN 4 25 OUTPL
GAIN0 5 24 PGND
GAIN1 6 23 OUTNL
AVCC 7 22 BSNL
AGND 8 21 BSNR
GVDD 9 20 OUTNR
PLIMIT 10 19 PGND
RINN 11 18 OUTPR
RINP 12 17 BSPR
NC 13 16 PVCCR
PBTL 14 15 PVCCR

Pin Functions
PIN
TYPE DESCRIPTION
NO. NAME
Shutdown logic input for audio amp (LOW = outputs Hi-Z, HIGH = outputs enabled). TTL logic levels
1 SD I
with compliance to AVCC.
Open drain output used to display short circuit or dc detect fault status. Voltage compliant to AVCC.
2 FAULT O Short circuit faults can be set to auto-recovery by connecting FAULT pin to SD pin. Otherwise, both
short circuit faults and dc detect faults must be reset by cycling PVCC.
3 LINP I Positive audio input for left channel. Biased at 3 V.
4 LINN I Negative audio input for left channel. Biased at 3 V.
5 GAIN0 I Gain select least significant bit. TTL logic levels with compliance to AVCC.
6 GAIN1 I Gain select most significant bit. TTL logic levels with compliance to AVCC.
7 AVCC P Analog supply
8 AGND — Analog signal ground. Connect to the thermal pad.
High-side FET gate drive supply. Nominal voltage is 7V. Also should be used as supply for PLIMIT
9 GVDD O
function.
Power limit level adjust. Connect a resistor divider from GVDD to GND to set power limit. Connect
10 PLIMIT I
directly to GVDD for no power limit.
11 RINN I Negative audio input for right channel. Biased at 3 V.
12 RINP I Positive audio input for right channel. Biased at 3 V.
13 NC — Not connected
14 PBTL I Parallel BTL mode switch

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Pin Functions (continued)

PIN
TYPE DESCRIPTION
NO. NAME
Power supply for right channel H-bridge. Right channel and left channel power supply inputs are
15 PVCCR P
connect internally.
Power supply for right channel H-bridge. Right channel and left channel power supply inputs are
16 PVCCR P
connect internally.
17 BSPR I Bootstrap I/O for right channel, positive high-side FET.
18 OUTPR O Class-D H-bridge positive output for right channel.
19 PGND — Power ground for the H-bridges.
20 OUTNR O Class-D H-bridge negative output for right channel.
21 BSNR I Bootstrap I/O for right channel, negative high-side FET.
22 BSNL I Bootstrap I/O for left channel, negative high-side FET.
23 OUTNL O Class-D H-bridge negative output for left channel.
24 PGND — Power ground for the H-bridges.
25 OUTPL O Class-D H-bridge positive output for left channel.
26 BSPL I Bootstrap I/O for left channel, positive high-side FET.
Power supply for left channel H-bridge. Right channel and left channel power supply inputs are
27 PVCCL P
connect internally.
Power supply for left channel H-bridge. Right channel and left channel power supply inputs are
28 PVCCL P
connect internally.

7 Specifications
7.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted) (1)
MIN MAX UNIT
VCC Supply voltage AVCC, PVCC –0.3 V 30 V V
VCC +
–0.3 V V
(2)
0.3 V
SD, GAIN0, GAIN1, PBTL, FAULT
< 10
VI Interface pin voltage V/ms
PLIMIT GVDD +
–0.3 V
0.3
RINN, RINP, LINN, LINP –0.3 6.3 V
See Thermal
Continuous total power dissipation
Information
BTL: PVCC > 15 V 4.8
RL Minimum Load Resistance BTL: PVCC ≤ 15 V 3.2
PBTL 3.2
TA Operating free-air temperature –40 85 °C
(3)
TJ Operating junction temperature range –40 150 °C
Tstg Storage temperature –65 150 °C

(1) Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under Recommended
Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
(2) The voltage slew rate of these pins must be restricted to no more than 10 V/ms. For higher slew rates, use a 100-kΩ resister in series
with the pins.
(3) The TPA3110D2 incorporates an exposed thermal pad on the underside of the chip. This acts as a heatsink, and it must be connected
to a thermally dissipating plane for proper power dissipation. Failure to do so may result in the device going into thermal protection
shutdown. See TI Technical Briefs SLMA002 for more information about using the TSSOP thermal pad.

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7.2 ESD Ratings

VALUE UNIT
Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001 (1) ±2000
V(ESD) Electrostatic discharge Charged-device model (CDM), per JEDEC specification JESD22- V
±500
C101 (2)

(1) JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process.
(2) JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process.

7.3 Recommended Operating Conditions

over operating free-air temperature range (unless otherwise noted)
MIN MAX UNIT
VCC Supply voltage PVCC, AVCC 8 26 V
VIH High-level input voltage SD, GAIN0, GAIN1, PBTL 2 V
VIL Low-level input voltage SD, GAIN0, GAIN1, PBTL 0.8 V
VOL Low-level output voltage FAULT, RPULL-UP= 100 k, VCC= 26 V 0.8 V
IIH High-level input current SD, GAIN0, GAIN1, PBTL, VI = 2 V, VCC = 18 V 50 µA
IIL Low-level input current SD, GAIN0, GAIN1, PBTL, VI = 0.8 V, VCC = 18 V 5 µA
TA Operating free-air temperature –40 85 °C

7.4 Thermal Information

TPA3110D2
THERMAL METRIC (1) PWP (HTSSOP) UNIT
28 PINS
RθJA Junction-to-ambient thermal resistance 30.3 °C/W
RθJC(top) Junction-to-case (top) thermal resistance 33.5 °C/W
RθJB Junction-to-board thermal resistance 17.5 °C/W
ψJT Junction-to-top characterization parameter 0.9 °C/W
ψJB Junction-to-board characterization parameter 7.2 °C/W
RθJC(bot) Junction-to-case (bottom) thermal resistance 0.9 °C/W

(1) For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report, SPRA953.

7.5 DC Characteristics: 24 V
TA = 25°C, VCC = 24 V, RL = 8 Ω (unless otherwise noted)
PARAMETER TEST CONDITIONS MIN TYP MAX UNIT
Class-D output offset voltage (measured
| VOS | VI = 0 V, Gain = 36 dB 1.5 15 mV
differentially)
ICC Quiescent supply current SD = 2 V, no load, PVCC = 24 V 32 50 mA
ICC(SD) Quiescent supply current in shutdown mode SD = 0.8 V, no load, PVCC = 24 V 250 400 µA
VCC = 12 V, IO = 500 mA, High Side 240
rDS(on) Drain-source on-state resistance mΩ
TJ = 25°C Low side 240
GAIN0 = 0.8 V 19 20 21
GAIN1 = 0.8 V dB
GAIN0 = 2 V 25 26 27
G Gain
GAIN0 = 0.8 V 31 32 33
GAIN1 = 2 V dB
GAIN0 = 2 V 35 36 37
ton Turn-on time SD = 2 V 14 ms
tOFF Turn-off time SD = 0.8 V 2 μs
GVDD Gate Drive Supply IGVDD = 100 μA 6.4 6.9 7.4 V
tDCDET DC Detect time V(RINN) = 6 V, VRINP = 0 V 420 ms

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7.6 DC Characteristics: 12 V
TA = 25°C, VCC = 12 V, RL = 8 Ω (unless otherwise noted)
PARAMETER TEST CONDITIONS MIN TYP MAX UNIT
Class-D output offset voltage (measured
| VOS | VI = 0 V, Gain = 36 dB 1.5 15 mV
differentially)
ICC Quiescent supply current SD = 2 V, no load, PVCC = 12V 20 35 mA
ICC(SD) Quiescent supply current in shutdown mode SD = 0.8 V, no load, PVCC = 12V 200 µA
VCC = 12 V, IO = 500 mA, High Side 240
rDS(on) Drain-source on-state resistance mΩ
TJ = 25°C Low side 240
GAIN0 = 0.8 V 19 20 21
GAIN1 = 0.8 V dB
GAIN0 = 2 V 25 26 27
G Gain
GAIN0 = 0.8 V 31 32 33
GAIN1 = 2 V dB
GAIN0 = 2 V 35 36 37
tON Turn-on time SD = 2 V 14 ms
tOFF Turn-off time SD = 0.8 V 2 μs
GVDD Gate Drive Supply IGVDD = 2 mA 6.4 6.9 7.4 V
Output Voltage maximum under PLIMIT
VO V(PLIMIT) = 2 V; VI = 1 V rms 6.75 7.90 8.75 V
control

7.7 AC Characteristics: 24 V
TA = 25°C, VCC = 24 V, RL = 8 Ω (unless otherwise noted)
PARAMETER TEST CONDITIONS MIN TYP MAX UNIT
200 mVPP ripple at 1 kHz,
KSVR Power Supply ripple rejection –70 dB
Gain = 20 dB, Inputs ac-coupled to AGND
PO Continuous output power THD+N = 10%, f = 1 kHz, VCC = 16 V 15 W
THD+N Total harmonic distortion + noise VCC = 16 V, f = 1 kHz, PO = 7.5 W (half-power) 0.1%
65 µV
Vn Output integrated noise 20 Hz to 22 kHz, A-weighted filter, Gain = 20 dB
–80 dBV
Crosstalk VO = 1 Vrms, Gain = 20 dB, f = 1 kHz –100 dB
Maximum output at THD+N < 1%, f = 1 kHz,
SNR Signal-to-noise ratio 102 dB
Gain = 20 dB, A-weighted
fOSC Oscillator frequency 250 310 350 kHz
Thermal trip point 150 °C
Thermal hysteresis 15 °C

7.8 AC Characteristics: 12 V
TA = 25°C, VCC = 12 V, RL = 8 Ω (unless otherwise noted)
PARAMETER TEST CONDITIONS MIN TYP MAX UNIT
200 mVPP ripple from 20 Hz–1 kHz,
KSVR Supply ripple rejection –70 dB
Gain = 20 dB, Inputs ac-coupled to AGND
PO Continuous output power THD+N = 10%, f = 1 kHz; VCC = 13 V 10 W
THD+N Total harmonic distortion + noise RL = 8 Ω, f = 1 kHz, PO = 5 W (half-power) 0.06%
65 µV
Vn Output integrated noise 20 Hz to 22 kHz, A-weighted filter, Gain = 20 dB
–80 dBV
Crosstalk Po = 1 W, Gain = 20 dB, f = 1 kHz –100 dB
Maximum output at THD+N < 1%, f = 1 kHz,
SNR Signal-to-noise ratio 102 dB
Gain = 20 dB, A-weighted
fOSC Oscillator frequency 250 310 350 kHz
Thermal trip point 150 °C
Thermal hysteresis 15 °C

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7.9 Typical Characteristics

All Measurements taken at 1 kHz, unless otherwise noted. Measurements were made using the TPA3110D2 EVM which is
available at www.ti.com.

10 10
Gain = 20 dB Gain = 20 dB
VCC = 12 V VCC = 18 V
ZL = 8 Ω + 66 µH ZL = 8Ω+ 66 µH

THD − Total Harmonic Distortion − %

THD − Total Harmonic Distortion − %

1 1

0.1 0.1
PO = 5 W PO = 10 W

PO = 1 W
0.01 PO = 0.5 W 0.01

PO = 2.5 W PO = 5 W

0.001 0.001
20 100 1k 10k 20k 20 100 1k 10k 20k
f − Frequency − Hz f − Frequency − Hz
G001 G002

Figure 1. Total Harmonic Distortion vs Frequency (BTL) Figure 2. Total Harmonic Distortion vs Frequency (BTL)
10 10
Gain = 20 dB Gain = 20 dB
VCC = 24 V VCC = 12 V
ZL = 8 Ω + 66 µH ZL = 6 Ω + 47 µH
THD − Total Harmonic Distortion − %
THD − Total Harmonic Distortion − %

1 1

0.1 PO = 10 W 0.1
PO = 5 W

PO = 1 W
PO = 0.5 W
0.01 0.01

PO = 2.5 W
PO = 5 W

0.001 0.001
20 100 1k 10k 20k 20 100 1k 10k 20k
f − Frequency − Hz f − Frequency − Hz
G003 G004

Figure 3. Total Harmonic Distortion vs Frequency (BTL) Figure 4. Total Harmonic Distortion vs Frequency (BTL)
10 10
Gain = 20 dB Gain = 20 dB
VCC = 18 V VCC = 12 V
ZL = 6 Ω + 47 µH ZL = 4 Ω + 33 µH
THD − Total Harmonic Distortion − %

THD − Total Harmonic Distortion − %

1 1

PO = 10 W
0.1 0.1 PO = 10 W

PO = 1 W
0.01 0.01
PO = 1 W
PO = 5 W
PO = 5 W

0.001 0.001
20 100 1k 10k 20k 20 100 1k 10k 20k
f − Frequency − Hz f − Frequency − Hz
G005 G006

Figure 5. Total Harmonic Distortion vs Frequency (BTL) Figure 6. Total Harmonic Distortion vs Frequency (BTL)

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Typical Characteristics (continued)

All Measurements taken at 1 kHz, unless otherwise noted. Measurements were made using the TPA3110D2 EVM which is
available at www.ti.com.
10 10
Gain = 20 dB Gain = 20 dB
THD+N − Total Harmonic Distortion + Noise − %

THD+N − Total Harmonic Distortion + Noise − %

VCC = 12 V VCC = 18 V
ZL = 8 Ω + 66 µH ZL = 8 Ω + 66 µH
1 1

f = 1 kHz f = 20 Hz
f = 20 Hz
0.1 f = 1 kHz 0.1

0.01 0.01

f = 10 kHz f = 10 kHz
0.001 0.001
0.01 0.1 1 10 50 0.01 0.1 1 10 50
PO − Output Power − W PO − Output Power − W
G007 G008

Figure 7. Total Harmonic Distortion + Noise vs Output Figure 8. Total Harmonic Distortion + Noise vs Output
Power (BTL) Power (BTL)
10 10
Gain = 20 dB Gain = 20 dB
THD+N − Total Harmonic Distortion + Noise − %

THD+N − Total Harmonic Distortion + Noise − %

VCC = 24 V VCC = 12 V
ZL = 8 Ω + 66 µH ZL = 6 Ω + 47 µH
1 1

f = 1 kHz
f = 1 kHz
f = 20 Hz
0.1 0.1

0.01 0.01

f = 20 Hz
f = 10 kHz f = 10 kHz

0.001 0.001
0.01 0.1 1 10 50 0.01 0.1 1 10 50
PO − Output Power − W PO − Output Power − W
G009 G010

Figure 9. Total Harmonic Distortion + Noise vs Output Figure 10. Total Harmonic Distortion + Noise vs Output
Power (BTL) Power (BTL)
10 10
Gain = 20 dB Gain = 20 dB
THD+N − Total Harmonic Distortion + Noise − %

THD+N − Total Harmonic Distortion + Noise − %

VCC = 18 V VCC = 12 V
ZL = 6 Ω + 47 µH ZL = 4 Ω + 33 µH
1 1

f = 1 kHz f = 1 kHz

f = 20 Hz
0.1 0.1

0.01 0.01

f = 20 Hz
f = 10 kHz
f = 10 kHz
0.001 0.001
0.01 0.1 1 10 50 0.01 0.1 1 10 50
PO − Output Power − W PO − Output Power − W
G011 G012

Figure 11. Total Harmonic Distortion + Noise vs Output Figure 12. Total Harmonic Distortion + Noise vs Output
Power (BTL) Power (BTL)

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Typical Characteristics (continued)

All Measurements taken at 1 kHz, unless otherwise noted. Measurements were made using the TPA3110D2 EVM which is
available at www.ti.com.
16 35
Gain = 20 dB Gain = 20 dB
14 VCC = 24 V VCC = 12 V
30
PO(Max) − Maximum Output Power − W

ZL = 8 Ω + 66 µH ZL = 4 Ω + 33 µH
12
25

PO − Output Power − W
10
20
8
15
6

10
4

2 5

0 0
0.0 0.5 1.0 1.5 2.0 2.5 3.0 0 1 2 3 4 5 6
VPLIMIT − PLIMIT Voltage − V VPLIMIT − PLIMIT Voltage − V
G013 G014

SPACE Note: Dashed Lines represent thermally limited regions.

Figure 13. Maximum Output Power vs PLIMIT Voltage (BTL) Figure 14. Output Power vs PLIMIT Voltage (BTL)
40 100 30
Gain = 20 dB
35 ZL = 8 Ω + 66 µH
50
25
Phase
30 0
PO − Output Power − W

20
25 −50
Gain − dB

Phase − °

THD = 10%
Gain
20 −100 15

THD = 1%
15 −150
CI = 1 µF 10
Gain = 20 dB
10 −200
Filter = Audio Precision AUX-0025
VCC = 12 V 5
5 VI = 0.1 Vrms −250
ZL = 8 Ω + 66 µH
0 −300 0
20 100 1k 10k 100k 6 8 10 12 14 16 18 20 22 24 26
f − Frequency − Hz VCC − Supply Voltage − V
G015 G016

SPACE Note: Dashed Lines represent thermally limited regions.

Figure 15. Gain and Phase vs Frequency (BTL) Figure 16. Output Power vs Supply Voltage (BTL)
25 100
Gain = 20 dB
90 VCC = 12 V VCC = 18 V
ZL = 4 Ω + 33 µH
VCC = 24 V
20 80
PO − Output Power − W

70
THD = 10%
h − Efficiency − %

15 60

50
THD = 1%
10 40

30

5 20

10 Gain = 20 dB
ZL = 8 Ω + 66 µH
0 0
6 8 10 12 14 16 18 0 5 10 15 20 25 30 35 40
VCC − Supply Voltage − V PO − Output Power − W
G017 G018

Note: Dashed Lines represent thermally limited regions. Note: Dashed Lines represent thermally limited regions.
Figure 17. Output Power vs Supply Voltage (BTL) Figure 18. Efficiency vs Output Power (BTL)

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Typical Characteristics (continued)

All Measurements taken at 1 kHz, unless otherwise noted. Measurements were made using the TPA3110D2 EVM which is
available at www.ti.com.
100 100
VCC = 12 V
90 VCC = 18 V 90 VCC = 12 V
VCC = 18 V
80 80
VCC = 24 V
70 70
h − Efficiency − %

h − Efficiency − %
60 60

50 50

40 40

30 30

20 20
Gain = 20 dB
10 LC Filter = 22 µH + 0.68 µF 10 Gain = 20 dB
RL = 8 Ω ZL = 6 Ω + 47 µH
0 0
0 5 10 15 20 25 0 5 10 15 20 25
PO − Output Power − W PO − Output Power − W
G032 G019

SPACE Note: Dashed Lines represent thermally limited regions.

Figure 19. Efficiency vs Output Power (BTL With LC Filter) Figure 20. Efficiency vs Output Power (BTL)
100 100

90 VCC = 12 V 90
VCC = 12 V
80 80
VCC = 18 V
70 70
h − Efficiency − %

h − Efficiency − %

60 60

50 50

40 40

30 30

20 20
Gain = 20 dB
10 LC Filter = 22 µH + 0.68 µF 10 Gain = 20 dB
RL = 6 Ω ZL = 4 Ω + 33 µH
0 0
0 5 10 15 20 25 0 3 6 9 12 15 18
PO − Output Power − W PO − Output Power − W
G033 G020

Figure 21. Efficiency vs Output Power (BTL With LC Filter) Figure 22. Efficiency vs Output Power (BTL)
100 2.6
2.4
90
VCC = 12 V 2.2 VCC = 18 V
80
2.0
ICC − Supply Current − A

70 1.8
h − Efficiency − %

60 1.6
VCC = 12 V
1.4
50
1.2 VCC = 24 V
40 1.0

30 0.8
0.6
20
Gain = 20 dB 0.4
10 LC Filter = 22 µH + 0.68 µF Gain = 20 dB
RL = 4 Ω 0.2 ZL = 8 Ω + 66 µH
0 0.0
0 5 10 15 20 25 0 5 10 15 20 25 30 35 40
PO − Output Power − W PO(Tot) − Total Output Power − W
G034 G021

SPACE Note: Dashed Lines represent thermally limited regions.

Figure 23. Efficiency vs Output Power (BTL With LC Filter) Figure 24. Supply Current vs Total Output Power (BTL)

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Typical Characteristics (continued)

All Measurements taken at 1 kHz, unless otherwise noted. Measurements were made using the TPA3110D2 EVM which is
available at www.ti.com.
3.2 −20
Gain = 20 dB Gain = 20 dB
−30
2.8 ZL = 4 Ω + 33 µH VCC = 12 V
−40 VO = 1 Vrms
ZL = 8 Ω + 66 µH
2.4
−50
ICC − Supply Current − A

2.0 −60

Crosstalk − dB
VCC = 12 V −70
1.6
−80
Right to Left
1.2 −90

−100
0.8
−110 Left to Right
0.4
−120

0.0 −130
0 5 10 15 20 25 30 20 100 1k 10k 20k
PO(Tot) − Total Output Power − W f − Frequency − Hz
G022 G023

Note: Dashed Lines represent thermally limited regions. SPACE

Figure 25. Supply Current vs Total Output Power (BTL) Figure 26. Crosstalk vs Frequency (BTL)
0 10
Gain = 20 dB Gain = 20 dB
Vripple = 200 mVpp VCC = 24 V
KSVR − Supply Ripple Rejection Ratio − dB

−20 ZL = 8 Ω + 66 µH ZL = 4 Ω + 33 µH
THD − Total Harmonic Distortion − %

1
−40 PO = 5 W

−60 VCC = 12 V 0.1

PO = 0.5 W
−80

0.01
−100 PO = 2.5 W

−120 0.001
20 100 1k 10k 20k 20 100 1k 10k 20k
f − Frequency − Hz f − Frequency − Hz
G024 G025

Figure 27. Supply Ripple Rejection Ratio vs Frequency Figure 28. Total Harmonic Distortion vs Frequency (PBTL)
(BTL)
10 40 100
Gain = 20 dB
THD+N − Total Harmonic Distortion + Noise − %

VCC = 24 V 35 50
ZL = 4 Ω + 33 µH
Phase
1 30 0
f = 1 kHz
25 −50
Gain − dB

Phase − °

Gain
0.1 20 −100

15 −150
CI = 1 µF
0.01 10 Gain = 20 dB
−200
Filter = Audio Precision AUX-0025
f = 20 Hz VCC = 24 V
5 VI = 0.1 Vrms −250
f = 10 kHz ZL = 8 Ω + 66 µH
0.001 0 −300
0.01 0.1 1 10 50 20 100 1k 10k 100k
PO − Output Power − W f − Frequency − Hz
G026 G027

Figure 29. Total Harmonic Distortion + Noise vs Output Figure 30. Gain and Phase vs Frequency (PBTL)
Power (PBTL)

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Typical Characteristics (continued)

All Measurements taken at 1 kHz, unless otherwise noted. Measurements were made using the TPA3110D2 EVM which is
available at www.ti.com.
40 100
Gain = 20 dB
ZL = 4 Ω + 33 µH 90
35
80
30 VCC = 18 V
PO − Output Power − W

70
VCC = 12 V

h − Efficiency − %
25
60
THD = 10%
20 50

THD = 1% 40
15
30
10
20
5 Gain = 20 dB
10
ZL = 4 Ω + 33 µH
0 0
6 8 10 12 14 16 18 20 0 5 10 15 20 25 30 35 40 45
VCC − Supply Voltage − V PO − Output Power − W
G028 G029

Note: Dashed Lines represent thermally limited regions. SPACE

Figure 31. Output Power vs Supply Voltage (PBTL) Figure 32. Efficiency vs Output Power (PBTL)
2.8 0
2.6 Gain = 20 dB Gain = 20 dB
ZL = 4 Ω + 33 µH Vripple = 200 mVpp
KSVR − Supply Ripple Rejection Ratio − dB
2.4
−20 ZL = 8 Ω + 66 µH
2.2
2.0
ICC − Supply Current − A

−40
1.8
1.6 VCC = 12 V
1.4 −60 VCC = 12 V
1.2 VCC = 18 V
1.0
−80
0.8
0.6
−100
0.4
0.2
0.0 −120
0 5 10 15 20 25 30 35 40 45 20 100 1k 10k 20k
PO − Output Power − W f − Frequency − Hz
G030 G031

Figure 33. Supply Current vs Output Power (PBTL) Figure 34. Supply Ripple Rejection Ratio vs Frequency
(PBTL)

8 Parameter Measurement Information

All parameters are measured according to the conditions described in the Specifications section.

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9 Detailed Description

9.1 Overview
The TPA3110D2 is a 15-W Class-D audio power amplifier. It is designed to drive BTL stereo speakers. This
device is able to use inexpensive ferrite bead filters at the outputs while meeting EMC requirements. The
TPA3110D2 can drive stereo speakers as low as 4 Ω and its high efficiency eliminates the need for an external
heat sink. The device is fully protected against shorts to GND, VCC and output-to-output. The short-circuit
protection and thermal protection includes an auto-recovery feature.

9.2 Functional Block Diagram

GVDD
PVCCL
BSPL
PVCCL

PBTL Select OUTPL FB

Gate
Drive OUTPL

OUTPL FB

LINP PGND
PWM
Gain
PLIMIT Logic
Control GVDD
LINN PVCCL
BSNL
PVCCL

OUTNL FB
OUTNL FB
FAULT
Gate
Drive OUTNL

SD
TTL
Buffer
GAIN0 SC Detect
Gain PGND
GAIN1 Control
DC Detect
Ramp Biases and Startup Protection
Generator References Logic Thermal
Detect
PLIMIT
PLIMIT Reference UVLO/OVLO

GVDD
PVCCL
BSNR
AVDD
PVCCL

AVCC LDO
Regulator

GVDD
Gate
Drive OUTNR
GVDD

OUTNN FB OUTNR FB

RINN
PGND
Gain PWM
PLIMIT Logic
Control
GVDD PVCCL
RINP
BSPR
PVCCL
OUTNP FB

Gate
Drive OUTPR
TTL PBTL PBTL Select
PBTL Buffer Select OUTPR FB

AGND
PGND

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9.3 Feature Description

9.3.1 TPA3110D2 Modulation Scheme
The TPA3110D2 uses a modulation scheme that allows operation without the classic LC reconstruction filter
when the amp is driving an inductive load. Each output is switching from 0 volts to the supply voltage. The OUTP
and OUTN are in phase with each other with no input so that there is little or no current in the speaker. The duty
cycle of OUTP is greater than 50% and OUTN is less than 50% for positive output voltages. The duty cycle of
OUTP is less than 50% and OUTN is greater than 50% for negative output voltages. The voltage across the load
sits at 0V throughout most of the switching period, reducing the switching current, which reduces any I2R losses
in the load.

OUTP

OUTN
No Output

OUTP
OUTP-OUTN 0V

Speaker
Current

OUTP

OUTN
Positive Output
PVCC
OUTP-OUTN 0V
Speaker
Current
0A

OUTP

Negative Output
OUTN

OUTP-OUTN 0V
-PVCC
Speaker 0A
Current

Figure 35. The TPA3110D2 Output Voltage And Current Waveforms Into An Inductive Load

9.3.1.1 Ferrite Bead Filter Considerations

Using the Advanced Emissions Suppression Technology in the TPA3110D2 amplifier it is possible to design a
high efficiency Class-D audio amplifier while minimizing interference to surrounding circuits. It is also possible to
accomplish this with only a low-cost ferrite bead filter. In this case it is necessary to carefully select the ferrite
bead used in the filter.
One important aspect of the ferrite bead selection is the type of material used in the ferrite bead. Not all ferrite
material is alike, so it is important to select a material that is effective in the 10 to 100 MHz range which is key to
the operation of the Class D amplifier. Many of the specifications regulating consumer electronics have
emissions limits as low as 30 MHz. It is important to use the ferrite bead filter to block radiation in the 30 MHz
and above range from appearing on the speaker wires and the power supply lines which are good antennas for
these signals. The impedance of the ferrite bead can be used along with a small capacitor with a value in the
range of 1000 pF to reduce the frequency spectrum of the signal to an acceptable level. For best performance,
the resonant frequency of the ferrite bead/ capacitor filter should be less than 10 MHz.

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Feature Description (continued)

Also, it is important that the ferrite bead is large enough to maintain its impedance at the peak currents expected
for the amplifier. Some ferrite bead manufacturers specify the bead impedance at a variety of current levels. In
this case it is possible to make sure the ferrite bead maintains an adequate amount of impedance at the peak
current the amplifier will see. If these specifications are not available, it is also possible to estimate the bead
current handling capability by measuring the resonant frequency of the filter output at low power and at maximum
power. A change of resonant frequency of less than fifty percent under this condition is desirable. Examples of
ferrite beads which have been tested and work well with the TPA3110D2 include 28L0138-80R-10 and
HI1812V101R-10 from Steward and the 742792510 from Wurth Electronics.
A high quality ceramic capacitor is also needed for the ferrite bead filter. A low ESR capacitor with good
temperature and voltage characteristics will work best.
Additional EMC improvements may be obtained by adding snubber networks from each of the class D outputs to
ground. Suggested values for a simple RC series snubber network would be 10 Ω in series with a 330 pF
capacitor although design of the snubber network is specific to every application and must be designed taking
into account the parasitic reactance of the printed circuit board as well as the audio amp. Take care to evaluate
the stress on the component in the snubber network especially if the amp is running at high PVCC. Also, make
sure the layout of the snubber network is tight and returns directly to the PGND or the PowerPAD™ beneath the
chip.
70
FCC Class B
60

50
Limit Level - dBmV/m

40

30

20

10

0
30M 230M 430M 630M 830M
f - Frequency - Hz

Figure 36. TPA3110D2 EMC Spectrum With FCC Class B Limits

9.3.1.2 Efficiency: LC Filter Required With The Traditional Class-D Modulation Scheme
The main reason that the traditional class-D amplifier needs an output filter is that the switching waveform results
in maximum current flow. This causes more loss in the load, which causes lower efficiency. The ripple current is
large for the traditional modulation scheme, because the ripple current is proportional to voltage multiplied by the
time at that voltage. The differential voltage swing is 2 × VCC, and the time at each voltage is half the period for
the traditional modulation scheme. An ideal LC filter is needed to store the ripple current from each half cycle for
the next half cycle, while any resistance causes power dissipation. The speaker is both resistive and reactive,
whereas an LC filter is almost purely reactive.
The TPA3110D2 modulation scheme has little loss in the load without a filter because the pulses are short and
the change in voltage is VCC instead of 2 × VCC. As the output power increases, the pulses widen, making the
ripple current larger. Ripple current could be filtered with an LC filter for increased efficiency, but for most
applications the filter is not needed.
An LC filter with a cutoff frequency less than the class-D switching frequency allows the switching current to flow
through the filter instead of the load. The filter has less resistance but higher impedance at the switching
frequency than the speaker, which results in less power dissipation, therefore increasing efficiency.

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Feature Description (continued)

9.3.1.3 When to Use an Output Filter for EMI Suppression
The TPA3110D2 has been tested with a simple ferrite bead filter for a variety of applications including long
speaker wires up to 125 cm and high power. The TPA3110D2 EVM passes FCC Class B specifications under
these conditions using twisted speaker wires. The size and type of ferrite bead can be selected to meet
application requirements. Also, the filter capacitor can be increased if necessary with some impact on efficiency.
There may be a few circuit instances where it is necessary to add a complete LC reconstruction filter. These
circumstances might occur if there are nearby circuits which are sensitive to noise. In these cases a classic
second order Butterworth filter similar to those shown in the figures below can be used.
Some systems have little power supply decoupling from the AC line but are also subject to line conducted
interference (LCI) regulations. These include systems powered by "wall warts" and "power bricks." In these
cases, it LC reconstruction filters can be the lowest cost means to pass LCI tests. Common mode chokes using
low frequency ferrite material can also be effective at preventing line conducted interference.
33 mH
OUTP
C2
L1
1 mF

33 mH
OUTN
C3
L2
1 mF

Figure 37. Typical LC Output Filter, Cutoff Frequency of 27 Khz, Speaker Impedance = 8 Ω

15 mH
OUTP
L1 C2
2.2 mF

15 mH
OUTN
L2 C3
2.2 mF

Figure 38. Typical Lc Output Filter, Cutoff Frequency Of 27 Khz, Speaker Impedance = 4 Ω

Ferrite
Chip Bead
OUTP

1 nF
Ferrite
Chip Bead
OUTN

1 nF

Figure 39. Typical Ferrite Chip Bead Filter (Chip Bead Example)

9.3.2 Gain Setting Via GAIN0 And GAIN1 Inputs

The gain of the TPA3110D2 is set by two input terminals, GAIN0 and GAIN1. The voltage slew rate of these gain
terminals, along with terminals 1 and 14, must be restricted to no more than 10V/ms. For higher slew rates, use
a 100kΩ resistor in series with the terminals.

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Feature Description (continued)

The gains listed in Table 1 are realized by changing the taps on the input resistors and feedback resistors inside
the amplifier. This causes the input impedance (ZI) to be dependent on the gain setting. The actual gain settings
are controlled by ratios of resistors, so the gain variation from part-to-part is small. However, the input impedance
from part-to-part at the same gain may shift by ±20% due to shifts in the actual resistance of the input resistors.
For design purposes, the input network (discussed in the next section) should be designed assuming an input
impedance of 7.2 kΩ, which is the absolute minimum input impedance of the TPA3110D2. At the lower gain
settings, the input impedance could increase as high as 72 kΩ

Table 1. Gain Setting

INPUT IMPEDANCE
AMPLIFIER GAIN (dB)
GAIN1 GAIN0 (kΩ)
TYP TYP
0 0 20 60
0 1 26 30
1 0 32 15
1 1 36 9

9.3.3 Differential Inputs

The differential input stage of the amplifier cancels any noise that appears on both input lines of the channel. To
use the TPA3110D2 with a differential source, connect the positive lead of the audio source to the INP input and
the negative lead from the audio source to the INN input. To use the TPA3110D2 with a single-ended source, ac
ground the INP or INN input through a capacitor equal in value to the input capacitor on INN or INP and apply
the audio source to either input. In a single-ended input application, the unused input should be ac grounded at
the audio source instead of at the device input for best noise performance. For good transient performance, the
impedance seen at each of the two differential inputs should be the same.
The impedance seen at the inputs should be limited to an RC time constant of 1 ms or less if possible. This is to
allow the input dc blocking capacitors to become completely charged during the 14 ms power-up time. If the input
capacitors are not allowed to completely charge, there will be some additional sensitivity to component matching
which can result in pop if the input components are not well matched.

9.3.4 PLIMIT
The voltage at pin 10 can used to limit the power to levels below that which is possible based on the supply rail.
Add a resistor divider from GVDD to ground to set the voltage at the PLIMIT pin. An external reference may also
be used if tighter tolerance is required. Also add a 1μF capacitor from pin 10 to ground.

Vinput

PLIMIT = 6.96V Pout = 11.8W

PLIMIT = 3V Pout = 10W

PLIMIT = 1.8V Pout = 5W

TPA3110D2 Power Limit Function

Vin=1.13VPP Freq=1kHz RLoad=8W

Figure 40. PLIMIT Circuit Operation

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The PLIMIT circuit sets a limit on the output peak-to-peak voltage. The limiting is done by limiting the duty cycle
to fixed maximum value. This limit can be thought of as a virtual voltage rail which is lower than the supply
connected to PVCC. This "virtual" rail is 4 times the voltage at the PLIMIT pin. This output voltage can be used to
calculate the maximum output power for a given maximum input voltage and speaker impedance.
2
ææ RL ö ö
çç ç ÷ x VP ÷÷
è RL + 2 x RS ø
POUT = è ø for unclipped power
2 x RL

Where:
• RS is the total series resistance including RDS(on), and any resistance in the output filter.
• RL is the load resistance.
• VP is the peak amplitude of the output possible within the supply rail.
• POUT (10%THD) = 1.25 × POUT (unclipped) (1)

Table 2. PLIMIT Typical Operation

OUTPUT VOLTAGE
TEST CONDITIONS PLIMIT VOLTAGE OUTPUT POWER (W)
AMPLITUDE (VP-P)
PVCC=24V, Vin=1Vrms, 6.97 36.1 (thermally limited) 43
RL=8Ω, Gain=26dB
PVCC=24V, Vin=1Vrms, 2.94 15 25.2
RL=8Ω, Gain=26dB
PVCC=24V, Vin=1Vrms, 2.34 10 20
RL=8Ω, Gain=26dB
PVCC=24V, Vin=1Vrms, 1.62 5 14
RL=8Ω, Gain=26dB
PVCC=24V, Vin=1Vrms, 6.97 12.1 27.7
RL=8Ω, Gain=20dB
PVCC=24V, Vin=1Vrms, 3.00 10 23
RL=8Ω, Gain=20dB
PVCC=24V, Vin=1Vrms, 1.86 5 14.8
RL=8Ω, Gain=20dB
PVCC=12V, Vin=1Vrms, 6.97 10.55 23.5
RL=8Ω, Gain=20dB
PVCC=12V, Vin=1Vrms, 1.76 5 15
RL=8Ω, Gain=20dB

9.3.5 GVDD Supply

The GVDD Supply is used to power the gates of the output full bridge transistors. It can also be used to supply
the PLIMIT voltage divider circuit. Add a 1-μF capacitor to ground at this pin.

9.3.6 PBTL Select

TPA3110D2 offers the feature of parallel BTL operation with two outputs of each channel connected directly. If
the PBTL pin (pin 14) is tied high, the positive and negative outputs of each channel (left and right) are
synchronized and in phase. To operate in this PBTL (mono) mode, apply the input signal to the RIGHT input and
place the speaker between the LEFT and RIGHT outputs. Connect the positive and negative output together for
best efficiency. The voltage slew rate of the PBTL pin must be restricted to no more than 10V/ms. For higher
slew rates, use a 100kΩ resistor in series with the terminals. For an example of the PBTL connection, see the
schematic in the APPLICATION INFORMATION section.
For normal BTL operation, connect the PBTL pin to local ground.

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9.3.7 Thermal Protection

Thermal protection on the TPA3110D2 prevents damage to the device when the internal die temperature
exceeds 150°C. There is a ±15°C tolerance on this trip point from device to device. Once the die temperature
exceeds the thermal set point, the device enters into the shutdown state and the outputs are disabled. This is not
a latched fault. The thermal fault is cleared once the temperature of the die is reduced by 15°C. The device
begins normal operation at this point with no external system interaction.
Thermal protection faults are NOT reported on the FAULT terminal.

9.3.8 DC Detect
TPA3110D2 has circuitry which will protect the speakers from DC current which might occur due to defective
capacitors on the input or shorts on the printed circuit board at the inputs. A DC detect fault will be reported on
the FAULT pin as a low state. The DC Detect fault will also cause the amplifier to shutdown by changing the
state of the outputs to Hi-Z. To clear the DC Detect it is necessary to cycle the PVCC supply. Cycling S D will
NOT clear a DC detect fault.
A DC Detect Fault is issued when the output differential duty-cycle of either channel exceeds 14% (for example,
+57%, -43%) for more than 420 msec at the same polarity. This feature protects the speaker from large DC
currents or AC currents less than 2Hz. To avoid nuisance faults due to the DC detect circuit, hold the SD pin low
at power-up until the signals at the inputs are stable. Also, take care to match the impedance seen at the positive
and negative inputs to avoid nuisance DC detect faults.
The minimum differential input voltages required to trigger the DC detect are show in table 2. The inputs must
remain at or above the voltage listed in the table for more than 420 msec to trigger the DC detect.

Table 3. DC Detect Threshold

AV(dB) Vin (mV, differential)
20 112
26 56
32 28
36 17

9.3.9 Short-Circuit Protection and Automatic Recovery Feature

TPA3110D2 has protection from overcurrent conditions caused by a short circuit on the output stage. The short
circuit protection fault is reported on the FAULT pin as a low state. The amplifier outputs are switched to a Hi-Z
state when the short circuit protection latch is engaged. The latch can be cleared by cycling the SD pin through
the low state.
If automatic recovery from the short circuit protection latch is desired, connect the FAULT pin directly to the SD
pin. This allows the FAULT pin function to automatically drive the SD pin low which clears the short-circuit
protection latch.

9.4 Device Functional Modes

9.4.1 SD Operation
The TPA3110D2 employs a shutdown mode of operation designed to reduce supply current (ICC) to the absolute
minimum level during periods of nonuse for power conservation. The SD input terminal should be held high (see
specification table for trip point) during normal operation when the amplifier is in use. Pulling SD low causes the
outputs to mute and the amplifier to enter a low-current state. Never leave SD unconnected, because amplifier
operation would be unpredictable.
For the best power-off pop performance, place the amplifier in the shutdown mode prior to removing the power
supply voltage.

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10 Application and Implementation

NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.

10.1 Application Information

This section describes a stereo BTL application and a mono PBTL application. In the stereo application the
Power Limiter is implemented, however in the mono application this limiter is not used.

10.2 Typical Applications

10.2.1 Stereo Class-D Amplifier With BTL Output and Single-Ended Inputs With Power Limiting

PVCC

100 μF 0.1 μF 1000 pF

100 kΩ
Control 1 28
SD PVCCL
System 1 kΩ
2 27
FAULT PVCCL
1 mF 3 26 0.22 μF
LINP BSPL FB
1 mF 4 25
LINN OUTPL 1000 pF

5 24
GAIN0 PGND
6 23
PVCC 10 Ω
GAIN1 OUTNL 1000 pF

7 22
AVCC BSNL FB
1 mF 0.22 μF
TPA3110D2
8 21 0.22 μF
AGND BSNR FB
1 mF 9 20 1000 pF
GVDD OUTNR
1 mF
10 kΩ 10 19
PLIMIT PGND
10 kΩ
1 mF 11 18
RINN OUTPR 1000 pF

Audio 12 17 FB
RINP BSPR
Source 1 mF
0.22 μF
13 16
NC PVCCR
100 μF 0.1 μF 1000 pF
14 15
PBTL PVCCR
GND
29
PowerPAD

PVCC

Figure 41. Typical Application Schematic With BTL Output and Single-Ended Inputs With Power Limiting

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Typical Applications (continued)

10.2.1.1 Design Requirements
For this design example, use the parameters listed in Table 4.

Table 4. Design Parameters

DESIGN PARAMETER EXAMPLE VALUE
Power supply 8 V to 26 V
High > 2 V
Shutdown, gain, and PBTL controls
Low < 0.8 V
Speaker impedance BTL 4 to 8 Ω
Speaker impedance PBTL 2 to 8 Ω

10.2.1.2 Detailed Design Procedure

10.2.1.2.1 Input Resistance

Changing the gain setting can vary the input resistance of the amplifier from its smallest value, 9 kΩ ±20%, to the
largest value, 60 kΩ ±20%. As a result, if a single capacitor is used in the input high-pass filter, the –3 dB or
cutoff frequency may change when changing gain steps.

Zf

Ci
Zi
Input IN
Signal

Figure 42. Input Impedance of the TPA3110D2

The –3-dB frequency can be calculated using Equation 2. Use the ZI values given in Table 1.
1
f =
2p Zi Ci (2)

10.2.1.2.2 Input Capacitor, CI

In the typical application, an input capacitor (CI) is required to allow the amplifier to bias the input signal to the
proper dc level for optimum operation. In this case, CI and the input impedance of the amplifier (ZI) form a high-
pass filter with the corner frequency determined in Equation 3.

-3 dB

1
fc =
2p Zi Ci

fc (3)
The value of CI is important, as it directly affects the bass (low-frequency) performance of the circuit. Consider
the example where ZI is 60 kΩ and the specification calls for a flat bass response down to 20 Hz. Equation 3 is
reconfigured as Equation 4.
1
Ci =
2p Zi fc (4)

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In this example, CI is 0.13 µF; so, one would likely choose a value of 0.15 μF as this value is commonly used. If
the gain is known and is constant, use ZI from Table 1 to calculate CI. A further consideration for this capacitor is
the leakage path from the input source through the input network (CI) and the feedback network to the load. This
leakage current creates a dc offset voltage at the input to the amplifier that reduces useful headroom, especially
in high gain applications. For this reason, a low-leakage tantalum or ceramic capacitor is the best choice. When
polarized capacitors are used, the positive side of the capacitor should face the amplifier input in most
applications as the dc level there is held at 3 V, which is likely higher than the source dc level. Note that it is
important to confirm the capacitor polarity in the application. Additionally, lead-free solder can create dc offset
voltages and it is important to ensure that boards are cleaned properly.

10.2.1.2.3 BSN and BSP Capacitors

The full H-bridge output stages use only NMOS transistors. Therefore, they require bootstrap capacitors for the
high side of each output to turn on correctly. A 0.22 μF ceramic capacitor, rated for at least 25 V, must be
connected from each output to its corresponding bootstrap input. Specifically, one 0.22 μF capacitor must be
connected from OUTPx to BSPx, and one 0.22 μF capacitor must be connected from OUTNx to BSNx. (See the
application circuit diagram in Figure 41.)
The bootstrap capacitors connected between the BSxx pins and corresponding output function as a floating
power supply for the high-side N-channel power MOSFET gate drive circuitry. During each high-side switching
cycle, the bootstrap capacitors hold the gate-to-source voltage high enough to keep the high-side MOSFETs
turned on.

10.2.1.2.4 Using Low-ESR Capacitors

Low-ESR capacitors are recommended throughout this application section. A real (as opposed to ideal) capacitor
can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this resistor
minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this resistance,
the more the real capacitor behaves like an ideal capacitor.

10.2.1.3 Application Curves

30 25
Gain = 20 dB Gain = 20 dB
ZL = 8 Ω + 66 µH ZL = 4 Ω + 33 µH
25
20
PO − Output Power − W

PO − Output Power − W

20
THD = 10%
15
THD = 10%
15
THD = 1%
THD = 1% 10
10

5
5

0 0
6 8 10 12 14 16 18 20 22 24 26 6 8 10 12 14 16 18
VCC − Supply Voltage − V VCC − Supply Voltage − V
G016 G017

Note: Dashed Lines represent thermally limited regions. Note: Dashed Lines represent thermally limited regions.
Figure 43. Output Power vs Supply Voltage (BTL) Figure 44. Output Power vs Supply Voltage (BTL)

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10.2.2 Stereo Class-D Amplifier With PBTL Output and Single-Ended Input

PVCC

100 μF 0.1 μF 1000 pF

100 kΩ
Control 1 28
SD PVCCL
System 1 kΩ
2 27
FAULT PVCCL
3 26
LINP BSPL
0.47 μF
4 25
LINN OUTPL
5 24
GAIN0 PGND
6 23 FB
AVCC GAIN1 OUTNL
1000 pF
7 22
PVCC AVCC BSNL
10 Ω TPA3110D2
1 mF 8 21
AGND BSNR
1000 pF
1 mF
9 20
GVDD OUTNR
FB
10 19
PLIMIT PGND
0.47 μF
1 mF 11 18
RINN OUTPR
Audio 12
BSPR
17
RINP
Source 1 mF
13 16
NC PVCCR
(1) 100 μF 0.1 μF 1000 pF
100 kW 14 15
AVCC PBTL
GND
PVCCR
29
PowerPAD

PVCC

(1) 100 kΩ resistor is needed if the PVCC slew rate is more than 10 V/ms.

Figure 45. Typical Application Schematic With PBTL Output and Single-Ended Input

10.2.3 Design Requirements

Refer to Table 4 for the Stereo Class-D Amplifier With PBTL Output and Single-Ended Input Application Design
Requirements.

10.2.4 Detailed Design Procedure

Refer to Detailed Design Procedure for the Stereo Class-D Amplifier With PBTL Output and Single-Ended Input
Application Detailed Design Procedure.

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10.2.5 Application Curve

40
Gain = 20 dB
35 ZL = 4 Ω + 33 µH

30

PO − Output Power − W
25
THD = 10%
20

THD = 1%
15

10

0
6 8 10 12 14 16 18 20
VCC − Supply Voltage − V
G028

Note: Dashed Lines represent thermally limited regions.

Figure 46. Output Power vs Supply Voltage (PBTL)

11 Power Supply Recommendations

The TPA3110D2 is designed to operate form an input voltage supply range between 8-V and 26-V. Therefore,
the output voltage range of power supply should be within this range and well regulated. The current capability of
upper power should not exceed the maximum current limit of the power switch.

11.1 Power Supply Decoupling, CS

The TPA3110D2 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling
to ensure that the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also
prevents oscillations for long lead lengths between the amplifier and the speaker. Optimum decoupling is
achieved by using a network of capacitors of different types that target specific types of noise on the power
supply leads. For higher frequency transients due to parasitic circuit elements such as bond wire and copper
trace inductances as well as lead frame capacitance, a good quality low equivalent-series-resistance (ESR)
ceramic capacitor of value between 220 pF and 1000 pF works well. This capacitor should be placed as close to
the device PVCC pins and system ground (either PGND pins or PowerPAD™) as possible.
For mid-frequency noise due to filter resonances or PWM switching transients as well as digital hash on the line,
another good quality capacitor typically 0.1 μF to 1 µF placed as close as possible to the device PVCC leads
works best. For filtering lower frequency noise signals, a larger aluminum electrolytic capacitor of 220 μF or
greater placed near the audio power amplifier is recommended.
The 220-μF capacitor also serves as a local storage capacitor for supplying current during large signal transients
on the amplifier outputs. The PVCC terminals provide the power to the output transistors, so a 220 µF or larger
capacitor should be placed on each PVCC terminal. A 10-µF capacitor on the AVCC terminal is adequate. Also,
a small decoupling resistor between AVCC and PVCC can be used to keep high frequency class D noise from
entering the linear input amplifiers.

12 Layout

12.1 Layout Guidelines

The TPA3110D2 can be used with a small, inexpensive ferrite bead output filter for most applications. However,
since the Class-D switching edges are fast, it is necessary to take care when planning the layout of the printed
circuit board. The following suggestions will help to meet EMC requirements.
• Decoupling capacitors—The high-frequency decoupling capacitors should be placed as close to the PVCC
and AVCC terminals as possible. Large (220 µF or greater) bulk power supply decoupling capacitors should
be placed near the TPA3110D2 on the PVCCL and PVCCR supplies. Local, high-frequency bypass
capacitors should be placed as close to the PVCC pins as possible. These caps can be connected to the
thermal pad directly for an excellent ground connection. Consider adding a small, good quality low ESR
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Layout Guidelines (continued)

ceramic capacitor between 220 pF and 1000 pF and a larger mid-frequency cap of value between 0.1μF and
1μF also of good quality to the PVCC connections at each end of the chip.
• Keep the current loop from each of the outputs through the ferrite bead and the small filter cap and back to
PGND as small and tight as possible. The size of this current loop determines its effectiveness as an
antenna.
• Grounding—The AVCC (pin 7) decoupling capacitor should be grounded to analog ground (AGND). The
PVCC decoupling capacitors should connect to PGND. Analog ground and power ground should be
connected at the thermal pad, which should be used as a central ground connection or star ground for the
TPA3110D2.
• Output filter—The ferrite EMI filter (Figure 39) should be placed as close to the output terminals as possible
for the best EMI performance. The LC filter (Figure 37 and Figure 38) should be placed close to the outputs.
The capacitors used in both the ferrite and LC filters should be grounded to power ground.
• Thermal Pad—The thermal pad must be soldered to the PCB for proper thermal performance and optimal
reliability. The dimensions of the thermal pad and thermal land should be 6.46mm by 2.35mm. Seven rows of
solid vias (three vias per row, 0,3302 mm or 13 mils diameter) should be equally spaced underneath the
thermal land. The vias should connect to a solid copper plane, either on an internal layer or on the bottom
layer of the PCB. The vias must be solid vias, not thermal relief or webbed vias. See the TI Application
Report SLMA002 for more information about using the TSSOP thermal pad. For recommended PCB
footprints, see figures at the end of this data sheet.
For an example layout, see the TPA3110D2 Evaluation Module (TPA3110D2EVM) User Manual. Both the EVM
user manual and the thermal pad application report are available on the TI Web site at www.ti.com.

12.2 Layout Example

Place Decoupling capacitors as

close to the device as possible.
1 nF 100 µF
0.1 nF
SD Bulk Capacitor for good
FB audio decoupling close to
FAULT Power source
1 µF
0.22 µF
LINP
OUTPL
1 µF FB
LINN 1 nF
330 pF 10
GAIN0
0.22 µF
GAIN1 OUTNL
1 µF FB
1 nF
Place Decoupling ` 330 pF 10
capacitors as close to OUTNR
the device as possible. 1 µF FB
1 nF
0.22 µF 10
PLIMIT 330 pF
1 µF
RINP OUTPR
FB
1 µF 1 nF
RINN 10
0.22 µF 330 pF
Several Via connection
PBTL between top and
FB
bottom ground layers
for EMI and Thermal
Vias on the thermal pad to get 1 nF 0.1 nF 100 µF performance
optimal thermal performance

Top Layer Ground Plane Top Layer Traces

Pad to Top Layer Ground Plane PowerPAD

Via to Ground Plane Via to Power

Figure 47. TPA3110D2 PCB Layout

Copyright © 2009–2015, Texas Instruments Incorporated Submit Documentation Feedback 25

Product Folder Links: TPA3110D2
TPA3110D2
SLOS528E – JULY 2009 – REVISED NOVEMBER 2015 www.ti.com

13 Device and Documentation Support

13.1 Device Support

13.1.1 Development Support
For the TPA3110D2 TINA-TI Reference Design, see SLAM052
For the TPA3110D2 TINA-TI Spice Model, see SLAM053

13.2 Documentation Support

13.2.1 Related Documentation
For related documentation see the following:
• Application Report, PowerPAD™ Thermally Enhanced Package, SLMA002
• Application Report, Using Thermal Calculation Tools for Analog Components, SLUA566
• Application Report, AN-1737 Managing EMI in Class D Audio Applications, SNAA050
• Application Report, AN-1849 An Audio Amplifier Power Supply Design, SNAA057
• Application Report, Guidelines for Measuring Audio Power Amplifier Performance, SLOA068
• User's Guide, TPA3110D2 EVM Audio Amplifier Evaluation Board SLOU263

13.3 Community Resources

The following links connect to TI community resources. Linked contents are provided "AS IS" by the respective
contributors. They do not constitute TI specifications and do not necessarily reflect TI's views; see TI's Terms of
Use.
TI E2E™ Online Community TI's Engineer-to-Engineer (E2E) Community. Created to foster collaboration
among engineers. At e2e.ti.com, you can ask questions, share knowledge, explore ideas and help
solve problems with fellow engineers.
Design Support TI's Design Support Quickly find helpful E2E forums along with design support tools and
contact information for technical support.

13.4 Trademarks
SpeakerGuard, PowerPAD, E2E are trademarks of Texas Instruments.
All other trademarks are the property of their respective owners.
13.5 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.

13.6 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.

14 Mechanical, Packaging, and Orderable Information

The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.

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 PACKAGE OPTION ADDENDUM

www.ti.com 15-Sep-2015

PACKAGING INFORMATION

Orderable Device Status Package Type Package Pins Package Eco Plan Lead/Ball Finish MSL Peak Temp Op Temp (°C) Device Marking Samples
(1) Drawing Qty (2) (6) (3) (4/5)

TPA3110D2PWP ACTIVE HTSSOP PWP 28 50 Green (RoHS CU NIPDAU Level-3-260C-168 HR -40 to 85 TPA3110D2
& no Sb/Br)
TPA3110D2PWPR ACTIVE HTSSOP PWP 28 2000 Green (RoHS CU NIPDAU Level-3-260C-168 HR -40 to 85 TPA3110D2
& no Sb/Br)

(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.

(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)

(3)
MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.

(4)
There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.

(5)
Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.

(6)
Lead/Ball Finish - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead/Ball Finish values may wrap to two lines if the finish
value exceeds the maximum column width.

Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.

Addendum-Page 1
 PACKAGE OPTION ADDENDUM

www.ti.com 15-Sep-2015

In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.

OTHER QUALIFIED VERSIONS OF TPA3110D2 :

• Automotive: TPA3110D2-Q1

NOTE: Qualified Version Definitions:

• Automotive - Q100 devices qualified for high-reliability automotive applications targeting zero defects

Addendum-Page 2
 PACKAGE MATERIALS INFORMATION

www.ti.com 15-Sep-2015

TAPE AND REEL INFORMATION

*All dimensions are nominal

Device Package Package Pins SPQ Reel Reel A0 B0 K0 P1 W Pin1
Type Drawing Diameter Width (mm) (mm) (mm) (mm) (mm) Quadrant
(mm) W1 (mm)
TPA3110D2PWPR HTSSOP PWP 28 2000 330.0 16.4 6.9 10.2 1.8 12.0 16.0 Q1

Pack Materials-Page 1
 PACKAGE MATERIALS INFORMATION

www.ti.com 15-Sep-2015

*All dimensions are nominal

Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm)
TPA3110D2PWPR HTSSOP PWP 28 2000 367.0 367.0 38.0

Pack Materials-Page 2
 IMPORTANT NOTICE

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