Integrated Synthesizer and VCO

ADF4360-7
FEATURES GENERAL DESCRIPTION
Output frequency range: 350 MHz to 1800 MHz The ADF4360-7 is an integrated integer-N synthesizer and
Divide-by-2 output voltage controlled oscillator (VCO). The ADF4360-7 center
3.0 V to 3.6 V power supply frequency is set by external inductors. This allows a frequency
1.8 V logic compatibility range of between 350 MHz to 1800 MHz. In addition, a divide-
Integer-N synthesizer by-2 option is available, whereby the user receives an RF output
Programmable dual-modulus prescaler 8/9, 16/17 of between 175 MHz and 900 MHz.
Programmable output power level
3-wire serial interface Control of all the on-chip registers is through a simple 3-wire
Analog and digital lock detect interface. The device operates with a power supply ranging from
Hardware and software power-down mode 3.0 V to 3.6 V and can be powered down when not in use.

APPLICATIONS
Wireless handsets (DECT, GSM, PCS, DCS, WCDMA)
Test equipment
Wireless LANs
CATV equipment
FUNCTIONAL BLOCK DIAGRAM
AVDD DVDD RSET CE

ADF4360-7

MULTIPLEXER MUXOUT
14-BIT R
REFIN COUNTER
LOCK
MUTE
DETECT
CLK
24-BIT
24-BIT
DATA FUNCTION
DATA REGISTER CHARGE
LATCH CP
LE PUMP
PHASE VVCO
COMPARATOR
VTUNE

L1
L2

CC
CN

INTEGER
REGISTER RFOUTA
VCO OUTPUT
CORE STAGE
13-BIT B
COUNTER RFOUTB

PRESCALER LOAD
P/P+1 LOAD
5-BIT A
COUNTER
N = (BP + A)
÷2
MULTIPLEXER

DIVSEL = 1

DIVSEL = 2
04441-001

AGND DGND CPGND

Figure 1.

Rev. A
Information furnished by Analog Devices is believed to be accurate and reliable.
However, no responsibility is assumed by Analog Devices for its use, nor for any
infringements of patents or other rights of third parties that may result from its use.
Specifications subject to change without notice. No license is granted by implication One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
or otherwise under any patent or patent rights of Analog Devices. Trademarks and Tel: 781.329.4700 www.analog.com
registered trademarks are the property of their respective owners. Fax: 781.326.8703 © 2004 Analog Devices, Inc. All rights reserved.
ADF4360-7

TABLE OF CONTENTS
Specifications..................................................................................... 3 Output Stage................................................................................ 12

Timing Characteristics..................................................................... 5 Latch Structure ........................................................................... 13

Absolute Maximum Ratings............................................................ 6 Power-Up..................................................................................... 17

Transistor Count........................................................................... 6 Control Latch .............................................................................. 19

ESD Caution.................................................................................. 6 N Counter Latch......................................................................... 20

Pin Configuration and Function Descriptions............................. 7 R Counter Latch ......................................................................... 20

Typical Performance Characteristics ............................................. 8 Applications..................................................................................... 21

Circuit Description......................................................................... 10 Frequency Generator ................................................................. 21

Reference Input Section............................................................. 10 Choosing the Correct Inductance Value ................................. 22

Prescaler (P/P + 1)...................................................................... 10 Fixed Frequency LO................................................................... 22

A and B Counters ....................................................................... 10 Interfacing ................................................................................... 23

R Counter .................................................................................... 10 PCB Design Guidelines for Chip Scale Package........................... 23

PFD and Charge Pump.............................................................. 10 Output Matching ........................................................................ 24

MUXOUT and Lock Detect...................................................... 11 Outline Dimensions ....................................................................... 25

Input Shift Register..................................................................... 11 Ordering Guide .......................................................................... 25

VCO.............................................................................................. 11

REVISION HISTORY
11/04—Rev. 0 to Rev. A.
Updated Format..................................................................Universal
Changes to General Description .................................................... 1
Changes to Specifications ................................................................ 3
Changes to the Reference Input Section...................................... 10
Changes to Power-Up Section ...................................................... 17
Added Table 10 ............................................................................... 17
Added Figure 22.............................................................................. 17
Updated Outline Dimensions ....................................................... 25

2/04—Revision 0: Initial Version.

Rev. A | Page 2 of 28
 ADF4360-7

SPECIFICATIONS1
AVDD = DVDD = VVCO = 3.3 V ± 10%; AGND = DGND = 0 V; TA = TMIN to TMAX, unless otherwise noted.
Table 1.
Parameter B Version Unit Conditions/Comments
REFIN CHARACTERISTICS
REFIN Input Frequency 10/250 MHz min/max For f < 10 MHz, use a dc-coupled CMOS-compatible
square wave, slew rate > 21 V/µs.
REFIN Input Sensitivity 0.7/AVDD V p-p min/max AC-coupled.
0 to AVDD V max CMOS compatible.
REFIN Input Capacitance 5.0 pF max
REFIN Input Current ±60 µA max
PHASE DETECTOR
Phase Detector Frequency2 8 MHz max
CHARGE PUMP
ICP Sink/Source3 With RSET = 4.7 kΩ.
High Value 2.5 mA typ
Low Value 0.312 mA typ
RSET Range 2.7/10 kΩ
ICP Three-State Leakage Current 0.2 nA typ
Sink and Source Current Matching 2 % typ 1.25 V ≤ VCP ≤ 2.5 V.
ICP vs. VCP 1.5 % typ 1.25 V ≤ VCP ≤ 2.5 V.
ICP vs. Temperature 2 % typ VCP = 2.0 V.
LOGIC INPUTS
VINH, Input High Voltage 1.5 V min
VINL, Input Low Voltage 0.6 V max
IINH/IINL, Input Current ±1 µA max
CIN, Input Capacitance 3.0 pF max
LOGIC OUTPUTS
VOH, Output High Voltage DVDD – 0.4 V min CMOS output chosen.
IOH, Output High Current 500 µA max
VOL, Output Low Voltage 0.4 V max IOL = 500 µA.
POWER SUPPLIES
AVDD 3.0/3.6 V min/V max
DVDD AVDD
VVCO AVDD
AIDD4 10 mA typ
DIDD4 2.5 mA typ
IVCO4, 5 14.0 mA typ ICORE = 5 mA.
IRFOUT4 3.5 to 11.0 mA typ RF output stage is programmable.
Low Power Sleep Mode 7 µA typ
Specifications continued on next page.

Rev. A | Page 3 of 28
ADF4360-7
Parameter B Version Unit Conditions/Comments
RF OUTPUT CHARACTERISTICS5
Maximum VCO Output Frequency 1800 MHz ICORE = 5 mA. Depending on L. See the Choosing the Correct
Inductance Value section.
Minimum VCO Output Frequency 350 MHz
VCO Output Frequency 490/585 MHz min/max L1, L2 = 13 nH. See the Choosing the Correct Inductance Value
section for other frequency values.
VCO Frequency Range 1.2 Ratio FMAX/FMIN
VCO Sensitivity 12 MHz/V typ L1, L2 = 13 nH. See the Choosing the Correct Inductance Value
section for other sensitivity values.
Lock Time6 400 µs typ To within 10 Hz of final frequency.
Frequency Pushing (Open Loop) 6 MHz/V typ
Frequency Pulling (Open Loop) 15 kHz typ Into 2.00 VSWR load.
Harmonic Content (Second) −19 dBc typ
Harmonic Content (Third) −9 dBc typ
Output Power5, 7 −14/−5 dBm typ Programmable in 3 dB steps. See Table 7.
Output Power Variation ±3 dB typ For tuned loads, see Output Matching section.
VCO Tuning Range 1.25/2.5 V min/max
NOISE CHARACTERISTIC5
VCO Phase-Noise Performance8 −116 dBc/Hz typ @ 100 kHz offset from carrier.
−138 dBc/Hz typ @ 1 MHz offset from carrier.
−144 dBc/Hz typ @ 3 MHz offset from carrier.
−148 dBc/Hz typ @ 10 MHz offset from carrier.
Synthesizer Phase-Noise Floor9 −172 dBc/Hz typ @ 25 kHz PFD frequency.
−163 dBc/Hz typ @ 200 kHz PFD frequency.
−147 dBc/Hz typ @ 8 MHz PFD frequency.
In-Band Phase Noise10, 11 −92 dBc/Hz typ @ 1 kHz offset from carrier.
RMS Integrated Phase Error12 0.3 Degrees typ 100 Hz to 100 kHz.
Spurious Signals due to PFD −70 dBc typ
Frequency11, 13

Level of Unlocked Signal with −44 dBm typ

MTLD Enabled

1
Operating temperature range is –40°C to +85°C.
2
Guaranteed by design. Sample tested to ensure compliance.
3
ICP is internally modified to maintain constant loop gain over the frequency range.
4
TA = 25°C; AVDD = DVDD = VVCO = 3.3 V; P = 32.
5
Unless otherwise stated, these characteristics are guaranteed for VCO core power = 5 mA. L1, L2 = 13 nH, 470 Ω resistors to GND in parallel with L1, L2.
6
Jumping from 490 MHz to 585 MHz. PFD frequency = 200 kHz; loop bandwidth = 10 kHz.
7
Using 50 Ω resistors to VVCO, into a 50 Ω load. For tuned loads, see the Output Matching section.
8
The noise of the VCO is measured in open-loop conditions.
9
The synthesizer phase-noise floor is estimated by measuring the in-band phase noise at the output of the VCO and subtracting 20 log N (where N is the N divider value).
10
The phase noise is measured with the EVAL-ADF4360-xEB1 Evaluation Board and the HP 8562E Spectrum Analyzer. The Spectrum Analyzer provides the REFIN for the
synthesizer; offset frequency = 1 kHz.
11
fREFIN = 10 MHz; fPFD = 200 kHz; N = 2500; loop B/W = 10 kHz.
12
fREFIN = 10 MHz; fPFD = 1 MHz; N = 500; loop B/W = 25 kHz.
13
The spurious signals are measured with the EVAL-ADF4360-xEB1 Evaluation Board and the HP 8562E Spectrum Analyzer. The Spectrum Analyzer provides the REFIN
for the synthesizer; fREFOUT = 10 MHz @ 0 dBm.

Rev. A | Page 4 of 28
 ADF4360-7

TIMING CHARACTERISTICS1
AVDD = DVDD = VVCO = 3.3 V ± 10%; AGND = DGND = 0 V; 1.8 V and 3 V logic levels used; TA = TMIN to TMAX, unless otherwise noted.
Table 2.
Parameter Limit at TMIN to TMAX (B Version) Unit Test Conditions/Comments
t1 20 ns min LE Setup Time
t2 10 ns min DATA to CLOCK Setup Time
t3 10 ns min DATA to CLOCK Hold Time
t4 25 ns min CLOCK High Duration
t5 25 ns min CLOCK Low Duration
t6 10 ns min CLOCK to LE Setup Time
t7 20 ns min LE Pulse Width

1
Refer to the Power-Up section for the recommended power-up procedure for this device.

t4 t5

CLOCK

t2 t3

DB1 DB0 (LSB)

DATA DB23 (MSB) DB22 DB2 (CONTROL BIT C2) (CONTROL BIT C1)

t7

LE

t1 t6

04441-002
LE

Figure 2. Timing Diagram

Rev. A | Page 5 of 28
ADF4360-7

ABSOLUTE MAXIMUM RATINGS

TA = 25°C, unless otherwise noted.
Table 3. Stresses above those listed under Absolute Maximum Ratings
Parameter Rating may cause permanent damage to the device. This is a stress rat-
AVDD to GND1 −0.3 V to +3.9 V ing only; functional operation of the device at these or any
AVDD to DVDD −0.3 V to +0.3 V other conditions above those listed in the operational sections
VVCO to GND −0.3 V to +3.9 V of this specification is not implied. Exposure to absolute maxi-
VVCO to AVDD −0.3 V to +0.3 V mum rating conditions for extended periods may affect device
Digital I/O Voltage to GND −0.3 V to VDD + 0.3 V reliability.
Analog I/O Voltage to GND −0.3 V to VDD + 0.3 V
REFIN to GND −0.3 V to VDD + 0.3 V This device is a high performance RF integrated circuit with an
Operating Temperature Range ESD rating of <1 kV, and it is ESD sensitive. Proper precautions
Maximum Junction Temperature 150°C should be taken for handling and assembly.
CSP θJA Thermal Impedance
Paddle Soldered 50°C/W
Paddle Not Soldered 88°C/W TRANSISTOR COUNT
Lead Temperature, Soldering
12543 (CMOS) and 700 (Bipolar)
Vapor Phase (60 sec) 215°C
Infrared (15 sec) 220°C

1
GND = AGND = DGND = 0 V.

ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate
on the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.

Rev. A | Page 6 of 28
 ADF4360-7

PIN CONFIGURATION AND FUNCTION DESCRIPTIONS

MUXOUT
AGND
DVDD
CP
CE

LE
24

23

22

21

20

19
PIN 1
CPGND 1 IDENTIFIER 18 DATA
AVDD 2 17 CLK
AGND 3 ADF4360-7 16 REFIN
TOP VIEW
RFOUTA 4 (Not to Scale) 15 DGND
RFOUTB 5 14 CN
VVCO 6 13 RSET

L2 10
AGND 11
CC 12
VTUNE 7
AGND 8
L1 9

04441-003
Figure 3. Pin Configuration
Table 4. Pin Function Descriptions
Pin No. Mnemonic Function
1 CPGND Charge Pump Ground. This is the ground return path for the charge pump.
2 AVDD Analog Power Supply. This ranges from 3.0 V to 3.6 V. Decoupling capacitors to the analog ground plane should be
placed as close as possible to this pin. AVDD must have the same value as DVDD.
3, 8, 11, 22 AGND Analog Ground. This is the ground return path of the prescaler and VCO.
4 RFOUTA VCO Output. The output level is programmable from −5 dBm to −14 dBm. See the Output Matching section for a
description of the various output stages.
5 RFOUTB VCO Complementary Output. The output level is programmable from −5 dBm to −14 dBm. See the Output Matching
section for a description of the various output stages.
6 VVCO Power Supply for the VCO. This ranges from 3.0 V to 3.6 V. Decoupling capacitors to the analog ground plane should
be placed as close as possible to this pin. VVCO must have the same value as AVDD.
7 VTUNE Control Input to the VCO. This voltage determines the output frequency and is derived from filtering the CP output
voltage.
9 L1 An external inductor to AGND should be connected to this pin to set the ADF4360-7 output frequency. L1 and L2
need to be the same value. For inductances greater than 3.3 nH, a 470 Ω resistor should be added in parallel to AGND.
10 L2 An external inductor to AGND should be connected to this pin to set the ADF4360-7 output frequency. L1 and L2
need to be the same value. For inductances greater than 3.3 nH, a 470 Ω resistor should be added in parallel to AGND.
12 CC Internal Compensation Node. This pin must be decoupled to ground with a 10 nF capacitor.
13 RSET Connecting a resistor between this pin and CPGND sets the maximum charge pump output current for the
synthesizer. The nominal voltage potential at the RSET pin is 0.6 V. The relationship between ICP and RSET is
11.75
I CPmax =
RSET
where RSET = 4.7 kΩ, and ICPmax = 2.5 mA.
14 CN Internal Compensation Node. This pin must be decoupled to VVCO with a 10 µF capacitor.
15 DGND Digital Ground.
16 REFIN Reference Input. This is a CMOS input with a nominal threshold of VDD/2 and a dc equivalent input resistance of
100 kΩ (see Figure 16). This input can be driven from a TTL or CMOS crystal oscillator, or it can be ac-coupled.
17 CLK Serial Clock Input. This serial clock is used to clock in the serial data to the registers. The data is latched into the 24-bit
shift register on the CLK rising edge. This input is a high impedance CMOS input.
18 DATA Serial Data Input. The serial data is loaded MSB first with the two LSBs being the control bits. This input is a high
impedance CMOS input.
19 LE Load Enable, CMOS Input. When LE goes high, the data stored in the shift registers is loaded into one of the four
latches, and the relevant latch is selected using the control bits.
20 MUXOUT This multiplexer output allows either the lock detect, the scaled RF, or the scaled reference frequency to be accessed
externally.
21 DVDD Digital Power Supply. This ranges from 3.0 V to 3.6 V. Decoupling capacitors to the digital ground plane should be
placed as close as possible to this pin. DVDD must have the same value as AVDD.
23 CE Chip Enable. A logic low on this pin powers down the device and puts the charge pump into three-state mode.
Taking the pin high powers up the device depending on the status of the power-down bits.
24 CP Charge Pump Output. When enabled, this provides ± ICP to the external loop filter, which in turn drives the internal VCO.

Rev. A | Page 7 of 28
ADF4360-7

TYPICAL PERFORMANCE CHARACTERISTICS

–40 0
VDD = 3.3V, VVCO = 3.3V
–50 –10 REFERENCE ICP = 2.5mA
LEVEL = –3.5dBm PFD FREQUENCY = 200kHz
–60 –20 LOOP BANDWIDTH = 10kHz
RES. BANDWIDTH = 30Hz
–70
OUTPUT POWER (dB)

–30 VIDEO BANDWIDTH = 30Hz

OUTPUT POWER (dB)

–80 SWEEP = 1.9 SECONDS
–40 AVERAGES = 10
–90
–50
–100
–60
–110
–70 –96.4dBc/Hz
–120

–130 –80

04441-007
04441-004
–140 –90

–150
100 1k 10k 100k 1M 10M –2kHz –1kHz 500MHz 1kHz 2kHz
FREQUENCY OFFSET (Hz)

Figure 4. Open-Loop VCO Phase Noise, L1, L2 = 13 nH Figure 7. Close-In Phase Noise at 500 MHz (200 kHz Channel Spacing)

–70 0
–75 VDD = 3.3V, VVCO = 3.3V
–10 REFERENCE ICP = 2.5mA
–80 LEVEL = –3dBm PFD FREQUENCY = 200kHz
–85 –20 LOOP BANDWIDTH = 10kHz
–90 RES. BANDWIDTH = 1kHz
OUTPUT POWER (dB)

–95 –30 VIDEO BANDWIDTH = 1kHz

OUTPUT POWER (dB)

AVERAGES = 20
–100
–40
–105
–110 –50
–115
–120 –60 –74dBc
–125 –70
–130
–135 –80
–140

04441-008
04441-005

–90
–145
–150
100 1k 10k 100k 1M 10M –0.25MHz –0.1MHz 1250MHz 0.1MHz 0.25MHz
FREQUENCY OFFSET (Hz)

Figure 5. VCO Phase Noise, 500 MHz, 200 kHz PFD, 10 kHz Loop Bandwidth Figure 8. Reference Spurs at 500 MHz
(200 kHz Channel Spacing, 10 kHz Loop Bandwidth)

–70 0
–75 VDD = 3.3V, VVCO = 3.3V
–10 REFERENCE ICP = 2.5mA
–80 LEVEL = –3dBm PFD FREQUENCY = 1MHz
–85 –20 LOOP BANDWIDTH = 25kHz
–90 RES. BANDWIDTH = 1kHz
–30 VIDEO BANDWIDTH = 1kHz
OUTPUT POWER (dB)

–95
OUTPUT POWER (dB)

SWEEP = 4.2 SECONDS

–100 AVERAGES = 20
–40
–105
–110 –50
–115
–60
–120
–79dBc
–125 –70
–130
–135 –80
04441-009

–140
04441-006

–90
–145
–150
100 1k 10k 100k 1M 10M –1.1MHz –0.55MHz 500MHz 0.55MHz 1.1MHz
FREQUENCY OFFSET (Hz)

Figure 6. VCO Phase Noise, 250 MHz, Figure 9. Reference Spurs at 500 MHz
Divide-by-2 Enabled 200 kHz PFD, 10 kHz Loop Bandwidth (1 MHz Channel Spacing, 25 kHz Loop Bandwidth)

Rev. A | Page 8 of 28
 ADF4360-7
–40 0
VDD = 3.3V, VVCO = 3.3V
–50 –10 REFERENCE ICP = 2.5mA
LEVEL = –3.5dBm PFD FREQUENCY = 200kHz
–60 –20 LOOP BANDWIDTH = 10kHz
RES. BANDWIDTH = 30Hz
–70
OUTPUT POWER (dB)

–30 VIDEO BANDWIDTH = 30Hz

OUTPUT POWER (dB)

–80 SWEEP = 1.9 SECONDS
–40 AVERAGES = 20
–90
–50
–100
–60 –87.5dBc/Hz
–110
–70
–120

–130 –80

04441-013
04441-010
–140 –90

–150
100 1k 10k 100k 1M 10M –2kHz –1kHz 1.25GHz 1kHz 2kHz
FREQUENCY OFFSET (Hz)

Figure 10. Open-Loop VCO Phase Noise, L1 and L2 = 1.0 nH Figure 13. Close-In Phase Noise at 1250 MHz (200 kHz Channel Spacing)

–70 0
–75 VDD = 3.3V, VVCO = 3.3V
–10 REFERENCE ICP = 2.5mA
–80 LEVEL = –3dBm PFD FREQUENCY = 200kHz
–85 –20 LOOP BANDWIDTH = 10kHz
–90 RES. BANDWIDTH = 1kHz
VIDEO BANDWIDTH = 1kHz
OUTPUT POWER (dB)

–95 –30

OUTPUT POWER (dB)

AVERAGES = 20
–100
–40
–105
–110 –50
–115
–60
–120
–125 –79dBc
–70
–130
–135 –80
–140

04441-014
04441-011

–90
–145
–150
100 1k 10k 100k 1M 10M –0.25MHz –0.1MHz 1250MHz 0.1MHz 0.25MHz
FREQUENCY OFFSET (Hz)

Figure 11. VCO Phase Noise, 1250 MHz, 200 kHz PFD, 10 kHz Loop Bandwidth Figure 14. Reference Spurs at 1250 MHz
(200 kHz Channel Spacing, 10 kHz Loop Bandwidth)

–70 0
–75 VDD = 3.3V, VVCO = 3.3V
–10 REFERENCE ICP = 2.5mA
–80 LEVEL = –3dBm PFD FREQUENCY = 1MHz
–85 –20 LOOP BANDWIDTH = 25kHz
–90 RES. BANDWIDTH = 1kHz
VIDEO BANDWIDTH = 1kHz
OUTPUT POWER (dB)

–95 –30
OUTPUT POWER (dB)

SWEEP = 4.2 SECONDS

–100 AVERAGES = 20
–40
–105
–110 –50
–115
–60
–120
–125 –79dBc
–70
–130
–135 –80
04441-015

–140
04441-012

–90
–145
–150
100 1k 10k 100k 1M 10M –1.1MHz –0.55MHz 1250MHz 0.55MHz 1.1MHz
FREQUENCY OFFSET (Hz)

Figure 12. VCO Phase Noise, 625 MHz, Figure 15. Reference Spurs at 1250 MHz
Divide-by-2 Enabled 200 kHz PFD, 10 kHz Loop Bandwidth (1 MHz Channel Spacing, 25 kHz Loop Bandwidth)

Rev. A | Page 9 of 28
ADF4360-7

CIRCUIT DESCRIPTION
REFERENCE INPUT SECTION
The reference input stage is shown in Figure 16. SW1 and SW2 N = BP + A
are normally closed switches. SW3 is normally open. When 13-BIT B TO PFD
COUNTER
power-down is initiated, SW3 is closed, and SW1 and SW2 are
LOAD
opened. This ensures that there is no loading of the REFIN pin PRESCALER
FROM VCO
on power-down. P/P+1
LOAD

POWER-DOWN MODULUS 5-BIT A

CONTROL CONTROL COUNTER

04441-017
NC 100kΩ N DIVIDER
SW2
REFIN NC TO R COUNTER
BUFFER Figure 17. A and B Counters
SW1 04441-016
SW3
NO
R COUNTER
The 14-bit R counter allows the input reference frequency to
Figure 16. Reference Input Stage be divided down to produce the reference clock to the phase
PRESCALER (P/P + 1) frequency detector (PFD). Division ratios from 1 to 16,383 are
allowed.
The dual-modulus prescaler (P/P + 1), along with the A and B
counters, enables the large division ratio, N, to be realized PFD AND CHARGE PUMP
(N = BP + A). The dual-modulus prescaler, operating at CML
The PFD takes inputs from the R counter and N counter
levels, takes the clock from the VCO and divides it down to a
(N = BP + A) and produces an output proportional to the phase
manageable frequency for the CMOS A and B counters. The
and frequency difference between them. Figure 18 is a simpli-
prescaler is programmable. It can be set in software to 8/9 or
fied schematic. The PFD includes a programmable delay ele-
16/17 and is based on a synchronous 4/5 core. A value of 32/33
ment that controls the width of the antibacklash pulse. This
can be programmed but it is not useful on this part. There is a
pulse ensures that there is no dead zone in the PFD transfer
minimum divide ratio possible for fully contiguous output
function and minimizes phase noise and reference spurs. Two
frequencies; this minimum is determined by P, the prescaler
bits in the R counter latch, ABP2 and ABP1, control the width of
value, and is given by (P2 − P).
the pulse (see Table 9).
A AND B COUNTERS VP
CHARGE
PUMP
The A and B CMOS counters combine with the dual-modulus
UP
prescaler to allow a wide range division ratio in the PLL feed- HI D1 Q1

back counter. The counters are specified to work when the U1

prescaler output is 300 MHz or less. Thus, with a VCO R DIVIDER

CLR1
frequency of 2.5 GHz, a prescaler value of 16/17 is valid, but a
value of 8/9 is not valid. At fundamental VCO frequencies less
than 700 MHz, a value of 8/9 is best. PROGRAMMABLE
DELAY
U3 CP

Pulse Swallow Function

ABP1 ABP2
The A and B counters, in conjunction with the dual-modulus
prescaler, make it possible to generate output frequencies that CLR2
DOWN
HI D2 Q2
are spaced only by the reference frequency divided by R. The
U2
VCO frequency equation is
N DIVIDER
CPGND
f VCO = [(P × B ) + A]× f REFIN /R
where: R DIVIDER

fVCO is the output frequency of the VCO.

N DIVIDER
P is the preset modulus of the dual-modulus prescaler
(8/9 or 16/17).
04441-018

CP OUTPUT
B is the preset divide ratio of the binary 13-bit counter (3 to 8191).
A is the preset divide ratio of the binary 5-bit swallow counter (0 to 31).
Figure 18. PFD Simplified Schematic and Timing (In Lock)
fREFIN is the external reference frequency oscillator.

Rev. A | Page 10 of 28
 ADF4360-7
MUXOUT AND LOCK DETECT Table 5. C2 and C1 Truth Table
The output multiplexer on the ADF4360 family allows the Control Bits
user to access various internal points on the chip. The state of C2 C1 Data Latch
MUXOUT is controlled by M3, M2, and M1 in the function 0 0 Control Latch
latch. The full truth table is shown in Table 7. Figure 19 shows 0 1 R Counter
the MUXOUT section in block diagram form. 1 0 N Counter (A and B)
1 1 Test Mode Latch
Lock Detect
MUXOUT can be programmed for two types of lock detect:
digital and analog. Digital lock detect is active high. When LDP
VCO
in the R counter latch is set to 0, digital lock detect is set high The VCO core in the ADF4360 family uses eight overlapping
when the phase error on three consecutive phase detector cycles bands, as shown in Figure 20, to allow a wide frequency range to
is less than 15 ns. be covered without a large VCO sensitivity (KV) and resultant
poor phase noise and spurious performance.
With LDP set to 1, five consecutive cycles of less than 15 ns
phase error are required to set the lock detect. It stays set high The correct band is chosen automatically by the band select
until a phase error of greater than 25 ns is detected on any logic at power-up or whenever the N counter latch is updated. It
subsequent PD cycle. is important that the correct write sequence be followed at
power-up. This sequence is:
The N-channel open-drain analog lock detect should be
operated with an external pull-up resistor of 10 kΩ nominal. 1. R counter latch
When a lock has been detected, this output is high with narrow 2. Control latch
low-going pulses. 3. N counter latch
DVDD
During band select, which takes five PFD cycles, the VCO VTUNE
is disconnected from the output of the loop filter and connected
ANALOG LOCK DETECT to an internal reference voltage.
DIGITAL LOCK DETECT
3.0
R COUNTER OUTPUT MUX CONTROL MUXOUT
N COUNTER OUTPUT
SDOUT 2.5
04441-019

VOLTAGE (V)

2.0
DGND

Figure 19. MUXOUT Circuit 1.5

INPUT SHIFT REGISTER

The ADF4360 family’s digital section includes a 24-bit input 1.0

shift register, a 14-bit R counter, and an 18-bit N counter

04441-020
comprised of a 5-bit A counter and a 13-bit B counter. Data is 0.5
450 500 550 600 650
clocked into the 24-bit shift register on each rising edge of CLK. FREQUENCY (MHz)
The data is clocked in MSB first. Data is transferred from the
Figure 20. Frequency vs. VTUNE, ADF4360-7
shift register to one of four latches on the rising edge of LE. The
destination latch is determined by the state of the two control The R counter output is used as the clock for the band select
bits (C2, C1) in the shift register. These are the two LSBs, DB1 logic and should not exceed 1 MHz. A programmable divider is
and DB0, shown in Figure 2. provided at the R counter input to allow division by 1, 2, 4, or 8 and
is controlled by Bits BSC1 and BSC2 in the R counter latch. Where
The truth table for these bits is shown in Table 5. Table 6 shows
the required PFD frequency exceeds 1 MHz, the divide ratio should
a summary of how the latches are programmed. Note that the
be set to allow enough time for correct band selection.
test mode latch is used for factory testing and should not be
programmed by the user.

Rev. A | Page 11 of 28
ADF4360-7
After band selection, normal PLL action resumes. The If the outputs are used individually, the optimum output stage
value of KV is determined by the value of inductors used consists of a shunt inductor to VDD.
(see the Choosing the Correct Inductance section). If divide-by-
2 operation has been selected (by programming DIV2 [DB22] Another feature of the ADF4360 family is that the supply current
high in the N counter latch), the value is halved. The ADF4360 to the RF output stage is shut down until the part achieves lock as
family contains linearization circuitry to minimize any variation measured by the digital lock detect circuitry. This is enabled by the
of the product of ICP and KV. mute-till-lock detect (MTLD) bit in the control latch.
RFOUTA RFOUTB
The operating current in the VCO core is programmable in four
steps: 5 mA, 10 mA, 15 mA, and 20 mA. This is controlled by
Bits PC1 and PC2 in the control latch.
VCO BUFFER/
OUTPUT STAGE DIVIDE BY 2

The RFOUTA and RFOUTB pins of the ADF4360 family are con-
nected to the collectors of an NPN differential pair driven by

04441-021
buffered outputs of the VCO, as shown in Figure 21. To allow
the user to optimize the power dissipation vs. the output power Figure 21. Output Stage ADF4360-7
requirements, the tail current of the differential pair is pro-
grammable via Bits PL1 and PL2 in the control latch. Four cur-
rent levels may be set: 3.5 mA, 5 mA, 7.5 mA, and 11 mA. These
levels give output power levels of −14 dBm, −11 dBm, −8 dBm,
and −5 dBm, respectively, using a 50 Ω resistor to VDD and ac
coupling into a 50 Ω load. Alternatively, both outputs can be
combined in a 1 + 1:1 transformer or a 180° microstrip coupler
(see the Output Matching section).

Rev. A | Page 12 of 28
 ADF4360-7
LATCH STRUCTURE
Table 6 shows the three on-chip latches for the ADF4360 family. The two LSBs decide which latch is programmed.

Table 6. Latch Structure

CONTROL LATCH

MUTE-TILL-

COUNTER
DETECTOR
POLARITY
CP GAIN
POWER-

POWER-
DOWN 2

DOWN 1

RESET
THREE-
OUTPUT CORE

PHASE
STATE
PRESCALER CURRENT CURRENT MUXOUT CONTROL

LD

CP
VALUE SETTING 2 SETTING 1 POWER CONTROL POWER BITS
LEVEL LEVEL

DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 DB2 DB1 DB0

P2 P1 PD2 PD1 CPI6 CPI5 CPI4 CPI3 CPI2 CPI1 PL2 PL1 MTLD CPG CP PDP M3 M2 M1 CR PC2 PC1 C2 (0) C1 (0)

N COUNTER LATCH

RESERVED
DIVIDE-BY-
2 SELECT

CP GAIN
DIVIDE-
BY-2

13-BIT B COUNTER 5-BIT A COUNTER CONTROL

BITS

DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 DB2 DB1 DB0

DIVSEL DIV2 CPG B13 B12 B11 B10 B9 B8 B7 B6 B5 B4 B3 B2 B1 RSV A5 A4 A3 A2 A1 C2 (1) C1 (0)

R COUNTER LATCH
RESERVED

RESERVED

PRECISION

ANTI-
DETECT

BAND
MODE

LOCK
TEST

BACKLASH CONTROL
BIT

SELECT 14-BIT REFERENCE COUNTER

PULSE BITS
CLOCK WIDTH

DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 DB2 DB1 DB0

04441-022
RSV RSV BSC2 BSC1 TMB LDP ABP2 ABP1 R14 R13 R12 R11 R10 R9 R8 R7 R6 R5 R4 R3 R2 R1 C2 (0) C1 (1)

Rev. A | Page 13 of 28
ADF4360-7

Table 7. Control Latch

MUTE-TILL-

COUNTER
DETECTOR
POLARITY
CP GAIN
POWER-

POWER-
DOWN 2

DOWN 1

RESET
THREE-
OUTPUT CORE

PHASE
STATE
PRESCALER CURRENT CURRENT MUXOUT CONTROL

LD

CP
VALUE SETTING 2 SETTING 1 POWER CONTROL POWER BITS
LEVEL LEVEL

DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 DB2 DB1 DB0

P2 P1 PD2 PD1 CPI6 CPI5 CPI4 CPI3 CPI2 CPI1 PL2 PL1 MTLD CPG CP PDP M3 M2 M1 CR PC2 PC1 C2 (0) C1 (0)

PC2 PC1 CORE POWER LEVEL

0 0 5mA
0 1 10mA
1 0 15mA
1 1 20mA

CPI6 CPI5 CPI4 ICP(mA) PHASE DETECTOR

CPI3 CPI2 CPI1 4.7kΩ PDP POLARITY
0 NEGATIVE COUNTER
0 0 0 0.31 CR OPERATION
1 POSITIVE
0 0 1 0.62 0 NORMAL
0 1 0 0.93 1 R, A, B COUNTERS
0 1 1 1.25 CHARGE PUMP HELD IN RESET
1 0 0 1.56 CP OUTPUT
1 0 1 1.87 0 NORMAL
1 1 0 2.18 1 THREE-STATE
1 1 1 2.50
CPG CP GAIN
0 CURRENT SETTING 1
1 CURRENT SETTING 2

MTLD MUTE-TILL-LOCK DETECT

0 DISABLED
1 ENABLED

PL2 PL1 OUTPUT POWER LEVEL M3 M2 M1 OUTPUT

CURRENT POWER INTO 50Ω (USING 50Ω TO VVCO) 0 0 0 THREE-STATE OUTPUT
0 0 1 DIGITAL LOCK DETECT
0 0 3.5mA –14dBm
(ACTIVE HIGH)
0 1 5.0mA –11dBm
0 1 0 N DIVIDER OUTPUT
1 0 7.5mA –8dBm
0 1 1 DVDD
1 1 11.0mA –5dBm
1 0 0 R DIVIDER OUTPUT
1 0 1 N-CHANNEL OPEN-DRAIN
LOCK DETECT
1 1 0 SERIAL DATA OUTPUT
1 1 1 DGND

CE PIN PD2 PD1 MODE

0 X X ASYNCHRONOUS POWER-DOWN
1 X 0 NORMAL OPERATION
1 0 1 ASYNCHRONOUS POWER-DOWN
1 1 1 SYNCHRONOUS POWER-DOWN

P2 P1 PRESCALER VALUE
0 0 8/9
0 1 16/17
04441-023

1 0 32/33
1 1 32/33

Rev. A | Page 14 of 28
 ADF4360-7

Table 8. N Counter Latch

RESERVED
DIVIDE-BY-
2 SELECT

CP GAIN
DIVIDE-
BY-2

13-BIT B COUNTER 5-BIT A COUNTER CONTROL

BITS

DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 DB2 DB1 DB0

DIVSEL DIV2 CPG B13 B12 B11 B10 B9 B8 B7 B6 B5 B4 B3 B2 B1 RSV A5 A4 A3 A2 A1 C2 (1) C1 (0)

THIS BIT IS NOT USED

BY THE DEVICE AND
IS A DON'T CARE BIT.

A COUNTER
A5 A4 .......... A2 A1 DIVIDE RATIO
0 0 .......... 0 0 0
0 0 .......... 0 1 1
0 0 .......... 1 0 2
0 0 .......... 1 1 3
. . .......... . . .
. . .......... . . .
. . .......... . . .
1 1 .......... 0 0 28
1 1 .......... 0 1 29
1 1 .......... 1 0 30
1 1 .......... 1 1 31

B13 B12 B11 B3 B2 B1 B COUNTER DIVIDE RATIO

0 0 0 .......... 0 0 0 NOT ALLOWED
0 0 0 .......... 0 0 1 NOT ALLOWED
0 0 0 .......... 0 1 0 NOT ALLOWED
0 0 0 .......... 1 1 1 3
. . . .......... . . . .
. . . .......... . . . .
. . . .......... . . . .
1 1 1 .......... 1 0 0 8188
1 1 1 .......... 1 0 1 8189
1 1 1 .......... 1 1 0 8190
1 1 1 .......... 1 1 1 8191

F4 (FUNCTION LATCH)
FASTLOCK ENABLE CP GAIN OPERATION
0 0 CHARGE PUMP CURRENT SETTING 1
IS PERMANENTLY USED
0 1 CHARGE PUMP CURRENT SETTING 2
IS PERMANENTLY USED

N = BP + A; P IS PRESCALER VALUE SET IN THE CONTROL LATCH.

04441-024

B MUST BE GREATER THAN OR EQUAL TO A. FOR CONTINUOUSLY

ADJACENT VALUES OF (N × FREF), AT THE OUTPUT, NMIN IS (P2–P).

DIV2 DIVIDE-BY-2
0 FUNDAMENTAL OUTPUT
1 DIVIDE-BY-2

DIVSEL DIVIDE-BY-2 SELECT (PRESCALER INPUT)

0 FUNDAMENTAL OUTPUT SELECTED
1 DIVIDE-BY-2 SELECTED

Rev. A | Page 15 of 28
ADF4360-7

Table 9. R Counter Latch

RESERVED

RESERVED

PRECISION
ANTI-

DETECT
BAND

MODE

LOCK
TEST
BACKLASH CONTROL

BIT
SELECT PULSE 14-BIT REFERENCE COUNTER
CLOCK BITS
WIDTH

DB23 DB22 DB21 DB20 DB19 DB18 DB17 DB16 DB15 DB14 DB13 DB12 DB11 DB10 DB9 DB8 DB7 DB6 DB5 DB4 DB3 DB2 DB1 DB0

RSV RSV BSC2 BSC1 TMB LDP ABP2 ABP1 R14 R13 R12 R11 R10 R9 R8 R7 R6 R5 R4 R3 R2 R1 C2 (0) C1 (1)

R14 R13 R12 R3 R2 R1 DIVIDE RATIO

0 0 0 .......... 0 0 1 1
0 0 0 .......... 0 1 0 2
0 0 0 .......... 0 1 1 3
TEST MODE 0 0 0 .......... 1 0 0 4
BIT SHOULD . . . .......... . . . .
BE SET TO 0 . . . .......... . . . .
THESE BITS ARE NOT FOR NORMAL
. . . .......... . . . .
USED BY THE DEVICE OPERATION.
1 1 1 .......... 1 0 0 16380
AND ARE DON'T CARE
1 1 1 .......... 1 0 1 16381
BITS.
1 1 1 .......... 1 1 0 16382
1 1 1 .......... 1 1 1 16383

ABP2 ABP1 ANTIBACKLASH PULSE WIDTH

0 0 3.0ns
0 1 1.3ns
1 0 6.0ns
1 1 3.0ns

LDP LOCK DETECT PRECISION

0 THREE CONSECUTIVE CYCLES OF PHASE DELAY LESS THAN
15ns MUST OCCUR BEFORE LOCK DETECT IS SET.
1 FIVE CONSECUTIVE CYCLES OF PHASE DELAY LESS THAN
15ns MUST OCCUR BEFORE LOCK DETECT IS SET.

BSC2 BSC1 BAND SELECT CLOCK DIVIDER

0 0 1
0 1 2
04441-025

1 0 4
1 1 8

Rev. A | Page 16 of 28
 ADF4360-7
POWER-UP During initial power-up, a write to the control latch powers up
Power-Up Sequence the part, and the bias currents of the VCO begin to settle. If
The correct programming sequence for the ADF4360-7 after these currents have not settled to within 10% of their steady-
power-up is: state value, and if the N counter latch is then programmed, the
VCO may not oscillate at the desired frequency, which does not
1. R counter latch allow the band select logic to choose the correct frequency
band, and the ADF4360-7 may not achieve lock. If the recom-
2. Control latch
mended interval is inserted, and the N counter latch is pro-
3. N counter latch grammed, the band select logic can choose the correct fre-
quency band, and the part locks to the correct frequency.
Initial Power-Up
Initial power-up refers to programming the part after the The duration of this interval is affected by the value of the
application of voltage to the AVDD, DVDD, VVCO and CE pins. On capacitor on the CN pin (Pin 14). This capacitor is used to
initial power-up, an interval is required between programming reduce the close-in noise of the ADF4360-7 VCO. The
the control latch and programming the N counter latch. This recommended value of this capacitor is 10 µF. Using this value
interval is necessary to allow the transient behavior of the requires an interval of ≥10 ms between the latching in of the
ADF4360-7 during initial power-up to settle. control latch bits and latching in of the N counter latch bits. If a
shorter delay is required, the capacitor can be reduced. A slight
phase noise penalty is incurred by this change, which is further
explained in the Table 10.

Table 10. CN Capacitance vs. Interval and Phase Noise

Recommended Interval Between Open-Loop Phase Noise @ 10 kHz Open-Loop Phase Noise @ 10 kHz
CN Value Control Latch and N Counter Latch Offset (L1 and L2 = 1.0 nH) Offset (L1 and L2 = 13.0 nH)
10 µF ≥10 ms −90 dBc −99 dBc
440 nF ≥ 600 µs −88 dBc −97 dBc

POWER-UP

CLOCK

R COUNTER CONTROL N COUNTER

DATA
LATCH DATA LATCH DATA LATCH DATA

LE
04441-026

REQUIRED INTERVAL
CONTROL LATCH WRITE TO
N COUNTER LATCH WRITE

Figure 22. ADF4360-7 Power-Up Timing

Rev. A | Page 17 of 28
ADF4360-7
Hardware Power-Up/Power-Down Software Power-Up/Power-Down
If the part is powered down via the hardware (using the CE pin) If the part is powered down via the software (using the control
and powered up again without any change to the N counter latch) and powered up again without any change to the N
register during power-down, the part locks at the correct fre- counter latch during power-down, the part locks at the correct
quency, because the part is already in the correct frequency frequency, because the part is already in the correct frequency
band. The lock time depends on the value of capacitance on the band. The lock time depends on the value of capacitance on the
CN pin, which is <10 ms for 10 µF capacitance. The smaller CN pin, which is <10 ms for 10 µF capacitance. The smaller
capacitance of 440 nF on this pin enables lock times of <600 µs. capacitance of 440 nF on this pin enables lock times of <600 µs.

The N counter value cannot be changed while the part is in The N counter value cannot be changed while the part is in
power-down, since the part may not lock to the correct power-down, because the part may not lock to the correct
frequency on power-up. If it is updated, the correct program- frequency on power-up. If it is updated, the correct program-
ming sequence for the part after power-up is the R counter ming sequence for the part after power-up is to the R counter
latch, followed by the control latch, and finally the N counter latch, followed by the control latch, and finally the N counter
latch, with the required interval between the control latch and N latch, with the required interval between the control latch and N
counter latch, as described in the Initial Power-Up section. counter latch, as described in the Initial Power-Up section.

Rev. A | Page 18 of 28
 ADF4360-7
CONTROL LATCH Charge Pump Currents
With (C2, C1) = (0,0), the control latch is programmed. Table 7 CPI3, CPI2, and CPI1 in the ADF4360 family determine
shows the input data format for programming the control latch. Current Setting 1.

Prescaler Value CPI6, CPI5, and CPI4 determine Current Setting 2. See the
In the ADF4360 family, P2 and P1 in the control latch set the truth table in Table 7.
prescaler values. Output Power Level
Power-Down Bits PL1 and PL2 set the output power level of the VCO. See the
DB21 (PD2) and DB20 (PD1) provide programmable power- truth table in Table 7.
down modes. Mute-Till-Lock Detect
In the programmed asynchronous power-down, the device DB11 of the control latch in the ADF4360 family is the mute-
powers down immediately after latching a 1 into Bit PD1, with till-lock detect bit. This function, when enabled, ensures that the
the condition that PD2 has been loaded with a 0. In the pro- RF outputs are not switched on until the PLL is locked.
grammed synchronous power-down, the device power-down is CP Gain
gated by the charge pump to prevent unwanted frequency DB10 of the control latch in the ADF4360 family is the charge
jumps. Once the power-down is enabled by writing a 1 into pump gain bit. When it is programmed to 1, Current Setting 2 is
Bit PD1 (on the condition that a 1 has also been loaded to PD2), used. When it is programmed to 0, Current Setting 1 is used.
the device goes into power-down on the second rising edge of
the R counter output, after LE goes high. When the CE pin is
Charge Pump Three-State
low, the device is immediately disabled regardless of the state of This bit puts the charge pump into three-state mode when
PD1 or PD2. programmed to a 1. It should be set to 0 for normal operation.
Phase Detector Polarity
When a power-down is activated (either synchronous or
asynchronous mode), the following events occur: The PDP bit in the ADF4360 family sets the phase detector
polarity. The positive setting enabled by programming a 1 is
• All active dc current paths are removed. used when using the on-chip VCO with a passive loop filter or
with an active noninverting filter. It can also be set to 0, which is
• The R, N, and timeout counters are forced to their load required if an active inverting loop filter is used.
state conditions.
MUXOUT Control
• The charge pump is forced into three-state mode. The on-chip multiplexer is controlled by M3, M2, and M1.
See the truth table in Table 7.
• The digital lock detect circuitry is reset.
Counter Reset
• The RF outputs are debiased to a high impedance state. DB4 is the counter reset bit for the ADF4360 family. When this
• The reference input buffer circuitry is disabled. is 1, the R counter and the A, B counters are reset. For normal
operation, this bit should be 0.
• The input register remains active and capable of loading and Core Power Level
latching data.
PC1 and PC2 set the power level in the VCO core. The recom-
mended setting is 5 mA. See the truth table in Table 7.

Rev. A | Page 19 of 28
ADF4360-7
N COUNTER LATCH R COUNTER LATCH
Table 8 shows the input data format for programming the With (C2, C1) = (0, 1), the R counter latch is programmed.
N counter latch. Table 9 shows the input data format for programming the
A Counter Latch R counter latch.

A5 to A1 program the 5-bit A counter. The divide range is R Counter

0 (00000) to 31 (11111). R1 to R14 set the counter divide ratio. The divide range is
Reserved Bits 1 (00......001) to 16383 (111......111).

DB7 is a spare bit that is reserved. It should be programmed to 0. Antibacklash Pulse Width
B Counter Latch DB16 and DB17 set the antibacklash pulse width.

B13 to B1 program the B counter. The divide range is 3 Lock Detect Precision
(00.....0011) to 8191 (11....111). DB18 is the lock detect precision bit. This bit sets the number of
Overall Divide Range reference cycles with less than 15 ns phase error for entering the
locked state. With LDP at 1, five cycles are taken; with LDP at 0,
The overall divide range is defined by ((P × B) + A), where P is
three cycles are taken.
the prescaler value.
Test Mode Bit
CP Gain
DB19 is the test mode bit (TMB) and should be set to 0. With
DB21 of the N counter latch in the ADF4360 family is the
TMB = 0, the contents of the test mode latch are ignored and
charge pump gain bit. When this is programmed to 1, Current
normal operation occurs as determined by the contents of the
Setting 2 is used. When programmed to 0, Current Setting 1 is used.
control latch, R counter latch, and N counter latch. Note that
This bit can also be programmed through DB10 of the control
test modes are for factory testing only and should not be pro-
latch. The bit always reflects the latest value written to it, whether
grammed by the user.
this is through the control latch or the N counter latch.
Band Select Clock
Divide-by-2
These bits set a divider for the band select logic clock input. The
DB22 is the divide-by-2 bit. When set to 1, the output divide-by-2
output of the R counter is by default the value used to clock the
function is chosen. When it is set to 0, normal operation occurs.
band select logic, but if this value is too high (>1 MHz), a
Divide-by-2 Select divider can be switched on to divide the R counter output to a
DB23 is the divide-by-2 select bit. When programmed to 1, the smaller value (see Table 9).
divide-by-2 output is selected as the prescaler input. When set Reserved Bits
to 0, the fundamental is used as the prescaler input. For exam-
DB23 to DB22 are spare bits that are reserved. They should be
ple, using the output divide-by-2 feature and a PFD frequency
programmed to 0.
of 200 kHz, the user needs a value of N = 5,000 to generate
500 MHz. With the divide-by-2 select bit high, the user may
keep N = 2,500.

Rev. A | Page 20 of 28
 ADF4360-7

APPLICATIONS
FREQUENCY GENERATOR
The wide frequency range of the AD4360-7, plus the on-chip This allows frequencies as low as 8 MHz and as high as
divider, make it an ideal choice for implementing any general 137 MHz to be generated using a single system. In the circuit
purpose clock generator or LO. drawn in Figure 23, the ADF4360-7 is being used to generate
1024 MHz, and the ADF4007 is being used to divide by 8. To
To implement a clock generator in the FM band, it is necessary provide a channel spacing of 100 kHz, a PFD frequency of
to use an external divider. The ADF4007 contains a hardware- 800 kHz is used for the ADF4360-7 PLL. The loop bandwidth
programmable N divider, allowing division ratios of 8, 16, 32, is chosen to be 20 kHz.
and 64. This divided-down signal is accessed from the
MUXOUT pin of the ADF4007. The output range of the system in Figure 23 is approximately
120 MHz to 135 MHz. The output phase noise is −104 dBc/Hz
The minimum frequency that can be fed to the ADF4007 is at 1 kHz offset. Using different inductor values allows the
500 MHz. Therefore, 2.2 nH inductors were used to set the ADF4360-7 to be used to synthesize any different range of
fundamental frequency of oscillation at 1 GHz, with a range frequencies over the operation of the part (235 MHz to
from 950 MHz to 1100 MHz. 1800 MHz).

VDD

LOCK
VVCO VDD DETECT
4.7kΩ
RSET CP VP VDD M2 M1
10µF 6 21 2 23 20 TO LO
VVCO DVDD AVDD CE MUXOUT VTUNE 7 PHASE PORT
13kΩ CHARGE
14 CN
CP 24 FREQUENCY MUX
1nF 1nF PUMP
DETECTOR MUXOUT
FREFIN 16 REFIN 6.8nF
51Ω 470pF 220pF
6.2kΩ
17 CLK
18 DATA ADF4360-7 ADF4007
VVCO
19 LE REFIN R COUNTER
SPI COMPATIBLE SERIAL BUS

12 CC ÷2
51Ω 51Ω
13 RSET 100pF RFINA
1nF
RFOUTA 4 N COUNTER
4.7kΩ ÷8, ÷16,
CPGND AGND DGND L1 L2 RF RFINB
OUTB 5 ÷32, ÷64

04441-027
1 3 8 11 22 15 9 10 100pF
2.2nH CPGND GND N1 N2

2.2nH

Figure 23. Frequency Generator

Rev. A | Page 21 of 28
ADF4360-7
35
CHOOSING THE CORRECT INDUCTANCE VALUE
The ADF4360-7 can be used at many different frequencies 30

simply by choosing the external inductors to give the correct

25

SENSITIVITY (MHz/V)
output frequency. Figure 24 shows a graph of both minimum
and maximum frequency vs. the external inductor value. The 20
correct inductor should cover the maximum and minimum
frequencies desired. The inductors used are the 0402 CS type 15

from Coilcraft. To reduce mutual coupling, the inductors should

10
be placed at right angles to one another.
5
As shown in Figure 24, the lowest commercially available value

04441-029
of inductance, 1.0 nH, sets the center frequency at approxi- 0
mately 1300 MHz. For inductances less than 2.4 nH, a PCB 0 10 20 30 40
EXT INDUCTANCE (nH)
trace should be used, a direct short. The lowest center
frequency of oscillation possible is approximately 350 MHz, Figure 25. Tuning Sensitivity (in MHz/V) vs. Inductance (nH)
which is achieved using 30 nH inductors. This relationship FIXED FREQUENCY LO
can be expressed by
Figure 26 shows the ADF4360-7 used as a fixed frequency LO at
1 500 MHz. The low-pass filter was designed using ADIsimPLL
FO =
2π 6.2 pF(0.9 nH + L EXT ) for a channel spacing of 8 MHz and an open-loop bandwidth of
30 kHz. The maximum PFD frequency of the ADF4360-7 is
where FO is the center frequency, and LEXT is the external induc- 8 MHz. Because using a larger PFD frequency allows the use of
tance. a smaller N, the in-band phase noise is reduced to as low as
possible, −109 dBc/Hz. The typical rms phase noise (100 Hz to
1500
100 kHz) of the LO in this configuration is 0.3°. The reference
1400
frequency is from a 16 MHz TCXO from Fox; thus, an R value of
1300
2 is programmed. Taking into account the high PFD frequency
1200
and its effect on the band select logic, the band select clock
FREQUENCY (MHz)

1100
divider is enabled. In this case, a value of 8 is chosen. A very sim-
1000
ple pull-up resistor and dc blocking capacitor complete the RF
900
output stage.
800
LOCK
700 VVCO VVDD DETECT
600
500 6 21 2 23 20
10µF
04441-028

400 VVCO DVDD AVDD CE MUXOUT VTUNE 7

14 CN 910Ω
FOX 1nF 1nF CP 24
300 801BE-160 16 REFIN
0 5 10 15 20 25 30 27nF
16MHz 51Ω 2.7nF 820pF
EXT INDUCTANCE (nH) 510Ω
17 CLK
ADF4360-7
Figure 24. Output Center Frequency vs. External Inductor Value 18 DATA
VVCO
19 LE
SPI COMPATIBLE SERIAL BUS

12 CC
The approximate value of capacitance at the midpoint of the 51Ω 51Ω
13 RSET 100pF
1nF
center band of the VCO is 6.2 pF, and the approximate value of 4.7kΩ
RFOUTA 4
CPGND AGND DGND L1 L2 RF
internal inductance due to the bond wires is 0.9 nH. The VCO 1 3 8 11 22 15 9
OUTB 5
10 100pF
sensitivity is a measure of the frequency change vs. the tuning 13nH

voltage. It is a very important parameter for the low-pass filter. 470Ω

Figure 25 shows a graph of the tuning sensitivity (in MHz/V) vs. 470Ω 13nH
04441-030

the inductance (nH). It can be seen that as the inductance

increases, the sensitivity decreases. This relationship can be
derived from the previous equation, i.e., because the inductance Figure 26. Fixed Frequency LO
has increased, the change in capacitance from the varactor has
less of an effect on the frequency.

Rev. A | Page 22 of 28
 ADF4360-7
INTERFACING ADSP-2181 Interface
The ADF4360 family has a simple SPI®-compatible serial inter- Figure 28 shows the interface between the ADF4360 family and
face for writing to the device. CLK, DATA, and LE control the the ADSP-21xx digital signal processor. The ADF4360 family
data transfer. When LE goes high, the 24 bits that have been needs a 24-bit serial word for each latch write. The easiest way
clocked into the appropriate register on each rising edge of CLK to accomplish this using the ADSP-21xx family is to use the
are transferred to the appropriate latch. See Figure 2 for the autobuffered transmit mode of operation with alternate fram-
timing diagram and Table 5 for the latch truth table. ing. This provides a means for transmitting an entire block of
serial data before an interrupt is generated.
The maximum allowable serial clock rate is 20 MHz. This
means that the maximum update rate possible is 833 kHz or
SCLOCK SCLK
one update every 1.2 µs. This is certainly more than adequate
MOSI SDATA
for systems that have typical lock times in hundreds of micro-
TFS LE ADF4360-x
seconds. ADSP-21xx
CE
I/O PORTS
ADuC812 Interface MUXOUT
(LOCK DETECT)
Figure 27 shows the interface between the ADF4360 family and

04441-032
the ADuC812 MicroConverter®. Because the ADuC812 is based
on an 8051 core, this interface can be used with any 8051-based Figure 28. ADSP-21xx to ADF4360-x Interface
microcontroller. The MicroConverter is set up for SPI master
mode with CPHA = 0. To initiate the operation, the I/O port Set up the word length for 8 bits and use three memory loca-
driving LE is brought low. Each latch of the ADF4360 family tions for each 24-bit word. To program each 24-bit latch, store
needs a 24-bit word, which is accomplished by writing three the 8-bit bytes, enable the autobuffered mode, and write to the
8-bit bytes from the MicroConverter to the device. After the transmit register of the DSP. This last operation initiates the
third byte has been written, the LE input should be brought autobuffer transfer.
high to complete the transfer.
PCB DESIGN GUIDELINES FOR CHIP SCALE PACKAGE
The leads on the chip scale package (CP-24) are rectangular.
SCLOCK SCLK The printed circuit board pad for these should be 0.1 mm
MOSI SDATA longer than the package lead length and 0.05 mm wider than
ADuC812 LE ADF4360-x the package lead width. The lead should be centered on the pad
I/O PORTS CE to ensure that the solder joint size is maximized.
MUXOUT
(LOCK DETECT)
The bottom of the chip scale package has a central thermal pad.
04441-031

The thermal pad on the printed circuit board should be at least

as large as this exposed pad. On the printed circuit board, there
Figure 27. ADuC812 to ADF4360-x Interface
should be a clearance of at least 0.25 mm between the thermal
I/O port lines on the ADuC812 are also used to control power- pad and the inner edges of the pad pattern to ensure that short-
down (CE input) and detect lock (MUXOUT configured as lock ing is avoided.
detect and polled by the port input). When operating in the
described mode, the maximum SCLOCK rate of the ADuC812 Thermal vias may be used on the printed circuit board thermal
is 4 MHz. This means that the maximum rate at which the out- pad to improve thermal performance of the package. If vias
put frequency can be changed is 166 kHz. are used, they should be incorporated into the thermal pad at a
1.2 mm pitch grid. The via diameter should be between 0.3 mm
and 0.33 mm, and the via barrel should be plated with 1 ounce
of copper to plug the via.

The user should connect the printed circuit thermal pad to

AGND. This is internally connected to AGND.

Rev. A | Page 23 of 28
ADF4360-7
VVCO
OUTPUT MATCHING
There are a number of ways to match the output of the 47nH

ADF4360-7 for optimum operation; the most basic is to use a 3.9pF 7.5nH
RFOUT
50 Ω resistor to VVCO. A dc bypass capacitor of 100 pF is con-

04441-034
50Ω
nected in series, as shown in Figure 29. Because the resistor is
not frequency dependent, this provides a good broadband
Figure 30. Optimum ADF4360-7 Output Stage
match. The output power in this circuit typically gives
−5 dBm output power into a 50 Ω load. If the user does not need the differential outputs available
VVCO
on the ADF4360-7, the user may either terminate the unused
output or combine both outputs using a balun. The circuit in
51Ω Figure 31 shows how best to combine the outputs.
100pF VVCO
RFOUT
04441-033

50Ω
9.0nH 47nH
7.5nH
Figure 29. Simple ADF4360-7 Output Stage RFOUTA 100pF
3.3pF

A better solution is to use a shunt inductor (acting as an RF 50Ω

9.0nH
choke) to VVCO. This gives a better match and, therefore, more RFOUTB
7.5nH

output power. Additionally, a series inductor is added after the

04441-035
3.3pF
dc bypass capacitor to provide a resonant LC circuit. This tunes
the oscillator output and provides approximately 10 dB addi- Figure 31. Balun for Combining ADF4360-7 RF Outputs
tional rejection of the second harmonic. The shunt inductor
needs to be a relatively high value (>40 nH). The circuit in Figure 31 is a lumped-lattice-type LC balun. It
is designed for a center frequency of 900 MHz and outputs
Experiments have shown that the circuit shown in Figure 30 5.0 dBm at this frequency. The series 7.5 nH inductor is used to
provides an excellent match to 50 Ω over a limited operating tune out any parasitic capacitance due to the board layout from
range of the ADF4360-7 (850 MHz to 950 MHz). This gives each input, and the remainder of the circuit is used to shift the
approximately −2 dBm output power across the specific output of one RF input by +90° and the second by −90°, thus
frequency range of the ADF4360-7 using 3.9 nH. For other combining the two. The action of the 9.0 nH inductor and the
frequencies, a tuned LC is recommended. Both complementary 3.3 pF capacitor accomplishes this. The 47 nH is used to provide
architectures can be examined using the EVAL-ADF4360-7EB1 an RF choke to feed the supply voltage, and the 100 pF capacitor
evaluation board. provides the necessary dc block. To ensure good RF perform-
ance, the circuits in Figure 30 and Figure 31 are implemented
with Coilcraft 0402/0603 inductors and AVX 0402 thin-film
capacitors.

Alternatively, instead of the LC balun shown in Figure 31, both

outputs may be combined using a 180° rat-race coupler.

Rev. A | Page 24 of 28
 ADF4360-7

OUTLINE DIMENSIONS

4.00 0.60 MAX

BSC SQ 0.60 MAX PIN 1
INDICATOR
19 24 1
0.50 18
PIN 1 *2.45
INDICATOR TOP BSC
3.75 EXPOSED
VIEW BSC SQ PAD 2.30 SQ
(BOTTOMVIEW) 2.15
0.50
13 6
0.40 12 7
0.30 0.23 MIN
0.80 MAX 2.50 REF
1.00 12° MAX 0.65 TYP
0.85 0.05 MAX
0.80 0.02 NOM

0.30 COPLANARITY
0.23 0.20 REF 0.08
SEATING
PLANE 0.18

*COMPLIANT TO JEDEC STANDARDS MO-220-VGGD-2

EXCEPT FOR EXPOSED PAD DIMENSION

Figure 32. 24-Lead Lead Frame Chip Scale Package [VQ_LFCSP]

4 mm × 4 mm Body, Very Thin Quad (CP-24-2)
Dimensions shown in millimeters

ORDERING GUIDE
Model Temperature Range Frequency Range Package Description Package Option
ADF4360-7BCP −40°C to +85°C 350 MHz to 1800 MHz 24-Lead VQ_LFCSP CP-24-2
ADF4360-7BCPRL −40°C to +85°C 350 MHz to 1800 MHz 24-Lead VQ_LFCSP CP-24-2
ADF4360-7BCPRL7 −40°C to +85°C 350 MHz to 1800 MHz 24-Lead VQ_LFCSP CP-24-2
ADF4360-7BCPZ1 −40°C to +85°C 350 MHz to 1800 MHz 24-Lead VQ_LFCSP CP-24-2
ADF4360-7BCPZRL1 −40°C to +85°C 350 MHz to 1800 MHz 24-Lead VQ_LFCSP CP-24-2
ADF4360-7BCPZRL71 −40°C to +85°C 350 MHz to 1800 MHz 24-Lead VQ_LFCSP CP-24-2
EVAL-ADF4360-7EB1 Evaluation Board

1
Z = Pb-free part.

Rev. A | Page 25 of 28
ADF4360-7

NOTES

Rev. A | Page 26 of 28
 ADF4360-7

NOTES

Rev. A | Page 27 of 28
ADF4360-7

NOTES

Purchase of licensed I2C components of Analog Devices or one of its sublicensed Associated Companies conveys a license for the purchaser under the Philips I2C Patent
Rights to use these components in an I2C system, provided that the system conforms to the I2C Standard Specification as defined by Philips.

© 2004 Analog Devices, Inc. All rights reserved. Trademarks and regis-
tered trademarks are the property of their respective owners.
D04441–0–11/04(A)

Rev. A | Page 28 of 28